# Base Station Antennas

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a theory about the antennas used in telecommunication system ,linear wire antennas

### Text of Base Station Antennas

• 184 LINEAR WIRE ANTENNAS

and the radiation resistance, for a free-space medium ( 120), is given by

4Cin(2) = 30(2.435) 73 (4-93)

The radiation resistance of (4-93) is also the radiation resistance at the input termi-nals (input resistance) since the current maximum for a dipole of l = /2 occurs at theinput terminals (see Figure 4.8). As it will be shown in Chapter 8, the imaginary part(reactance) associated with the input impedance of a dipole is a function of its length(for l = /2, it is equal to j42.5). Thus the total input impedance for l = /2 is equal to

Zin = 73 + j42.5 (4-93a)

To reduce the imaginary part of the input impedance to zero, the antenna is matchedor reduced in length until the reactance vanishes. The latter is most commonly usedin practice for half-wavelength dipoles.

Depending on the radius of the wire, the length of the dipole for rst resonanceis about l = 0.47 to 0.48; the thinner the wire, the closer the length is to 0.48.Thus, for thicker wires, a larger segment of the wire has to be removed from /2 toachieve resonance.

4.7 LINEAR ELEMENTS NEAR OR ON INFINITE PERFECT CONDUCTORS

Thus far we have considered the radiation characteristics of antennas radiating into anunbounded medium. The presence of an obstacle, especially when it is near the radiatingelement, can signicantly alter the overall radiation properties of the antenna system.In practice the most common obstacle that is always present, even in the absence ofanything else, is the ground. Any energy from the radiating element directed towardthe ground undergoes a reection. The amount of reected energy and its direction arecontrolled by the geometry and constitutive parameters of the ground.

In general, the ground is a lossy medium ( = 0) whose effective conductivityincreases with frequency. Therefore it should be expected to act as a very good conduc-tor above a certain frequency, depending primarily upon its composition and moisturecontent. To simplify the analysis, it will rst be assumed that the ground is a perfectelectric conductor, at, and innite in extent. The effects of nite conductivity andearth curvature will be incorporated later. The same procedure can also be used toinvestigate the characteristics of any radiating element near any other innite, at,perfect electric conductor. Although innite structures are not realistic, the developedprocedures can be used to simulate very large (electrically) obstacles. The effects thatnite dimensions have on the radiation properties of a radiating element can be conve-niently accounted for by the use of the Geometrical Theory of Diffraction (Chapter 12,Section 12.10) and/or the Moment Method (Chapter 8, Section 8.4).4.7.1 Image TheoryTo analyze the performance of an antenna near an innite plane conductor, virtualsources (images) will be introduced to account for the reections. As the name implies,these are not real sources but imaginary ones, which when combined with the real

• LINEAR ELEMENTS NEAR OR ON INFINITE PERFECT CONDUCTORS 185

Actualsource

Direct

DirectReflected

Virtual source(image)

(a) Vertical electric dipole

Reflected

=

i2 r2

r1 i1

P1

P2

h

h

R2R1

Direct

(b) Field components at point of reflection

Reflected

=

h

h

n^ Er2Er1

E 2E 1

0, 0

Figure 4.12 Vertical electric dipole above an innite, at, perfect electric conductor.

sources, form an equivalent system. For analysis purposes only, the equivalent systemgives the same radiated eld on and above the conductor as the actual system itself.Below the conductor, the equivalent system does not give the correct eld. However,in this region the eld is zero and there is no need for the equivalent.

To begin the discussion, let us assume that a vertical electric dipole is placed adistance h above an innite, at, perfect electric conductor as shown in Figure 4.12(a).The arrow indicates the polarity of the source. Energy from the actual source is radi-ated in all directions in a manner determined by its unbounded medium directionalproperties. For an observation point P1, there is a direct wave. In addition, a wavefrom the actual source radiated toward point R1 of the interface undergoes a reection.

• 186 LINEAR WIRE ANTENNAS

The direction is determined by the law of reection ( i1 = r1 ) which assures that theenergy in homogeneous media travels in straight lines along the shortest paths. Thiswave will pass through the observation point P1. By extending its actual path below theinterface, it will seem to originate from a virtual source positioned a distance h belowthe boundary. For another observation point P2 the point of reection is R2, but thevirtual source is the same as before. The same is concluded for all other observationpoints above the interface.

The amount of reection is generally determined by the respective constitutiveparameters of the media below and above the interface. For a perfect electric conductorbelow the interface, the incident wave is completely reected and the eld below theboundary is zero. According to the boundary conditions, the tangential components ofthe electric eld must vanish at all points along the interface. Thus for an incidentelectric eld with vertical polarization shown by the arrows, the polarization of thereected waves must be as indicated in the gure to satisfy the boundary conditions. Toexcite the polarization of the reected waves, the virtual source must also be verticaland with a polarity in the same direction as that of the actual source (thus a reectioncoefcient of +1).

Another orientation of the source will be to have the radiating element in a horizontalposition, as shown in Figure 4.24. Following a procedure similar to that of the verticaldipole, the virtual source (image) is also placed a distance h below the interface butwith a 180 polarity difference relative to the actual source (thus a reection coefcientof 1).

In addition to electric sources, articial equivalent magnetic sources and magneticconductors have been introduced to aid in the analyses of electromagnetic boundary-value problems. Figure 4.13(a) displays the sources and their images for an electricplane conductor. The single arrow indicates an electric element and the double amagnetic one. The direction of the arrow identies the polarity. Since many problemscan be solved using duality, Figure 4.13(b) illustrates the sources and their imageswhen the obstacle is an innite, at, perfect magnetic conductor.

4.7.2 Vertical Electric Dipole

The analysis procedure for vertical and horizontal electric and magnetic elements nearinnite electric and magnetic plane conductors, using image theory, was illustratedgraphically in the previous section. Based on the graphical model of Figure 4.12, themathematical expressions for the elds of a vertical linear element near a perfectelectric conductor will now be developed. For simplicity, only far-eld observationswill be considered.

Referring to the geometry of Figure 4.14(a), the far-zone direct component of theelectric eld of the innitesimal dipole of length l, constant current I0, and observationpoint P is given according to (4-26a) by

Ed = jkI0le

jkr1

4r1sin 1 (4-94)

The reected component can be accounted for by the introduction of the virtual source(image), as shown in Figure 4.14(a), and it can be written as

Er = jRvkI0le

jkr2

4r2sin 2 (4-95)

• LINEAR ELEMENTS NEAR OR ON INFINITE PERFECT CONDUCTORS 187

Figure 4.13 Electric and magnetic sources and their images near electric (PEC) andmagnetic (PMC) conductors.

or

Er = jkI0le

jkr2

4r2sin 2 (4-95a)

since the reection coefcient Rv is equal to unity.The total eld above the interface (z 0) is equal to the sum of the direct and

reected components as given by (4-94) and (4-95a). Since a eld cannot exist insidea perfect electric conductor, it is equal to zero below the interface. To simplify theexpression for the total electric eld, it is referred to the origin of the coordinate system(z = 0).

In general, we can write that

r1 = [r2 + h2 2rh cos ]1/2 (4-96a)r2 = [r2 + h2 2rh cos( )]1/2 (4-96b)

• 188 LINEAR WIRE ANTENNAS

z P

y

x

r1q1

q2

q

y

f

r2

(a) Vertical electric dipole above ground plane

r

h

hs =

z

y

x

r1

qi

q

y

f

r2

r

(b) Far-field observations

h

hs =

Figure 4.14 Vertical electric dipole above innite perfect electric conductor.

For far-eld observations (r h), (4-96a) and (4-96b) reduce using the binomialexpansion to

r1 r h cos (4-97a)r2 r + h cos (4-97b)

As shown in Figure 4.14(b), geometrically (4-97a) and (4-97b) represent parallel lines.Since the amplitude variations are not as critical

r1 r2 r for amplitude variations (4-98)

• LINEAR ELEMENTS NEAR OR ON INFINITE PERFECT CONDUCTORS 189

Using (4-97a)(4-98), the sum of (4-94) and (4-95a) can be written as

E jkI0lejkr

4rsin [2 cos(kh cos )] z 0

E = 0 z < 0

(4-99)

It is evident that the total electric eld is equal to the product of the eld of a singlesource positioned symmetrically about the origin and a factor [within the brackets in(4-99)] which is a function of the antenna height (h) and the observation angle ().This is referred to as pattern multiplication and the factor is known as the array factor[see also (6-5)]. This will be developed and discussed in more detail and for morecomplex congurations in Chapter 6.

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