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1E13ETRANSACTIONSON MfCROWAVETIilZORYAND TECHNIQUm, VOl,. MTT-19, NO. i 1, NOV13v15ER197i 843
A Precision Compact Rotary Vane Attenuator
TOM Y. OTOSHI, iW3MBER, IEEE, AND CHARLES T. STELZRIED, MEMBER, IEEE
Absfracf—The accurate attenuation range of many precision
rotary vane attenuators is fimited to about 40 dB because of a trans-mission error term that is not accounted for in the familiar COS2
@attenuation law. This paper presents a modified law that makes it
possible to extend the useful dynamic attenuation range. The samemodified law also makes it practical to reduce the length of the rotor
section and, therefore, to develop compact rotary vane attenuators
that are accurate over reduced dynamic attenuation ranges. Themodified law requires the additional calibrations of the incremental
attenuation and incremental phase change at the 90° vane anglesetting.
To verify the modified law, a precision compact WR 112 rotaryvane attenuator was fabricated and tested. The attenuator has a
totaf dynamic attenuation range of about 30 dB and a rotor section
length approximately one-third that of a conventional WR 112attenuator. Application of the modified law resulted in good agree-
ment between theoretical and measured incremental attenuations
over the total dynamic attenuation range.
1. INTRODUCTION
I
N RECENT years, a great deal of attention has
been focused on the development of high-precision
rotary vane attenuators (RVAS) for use as primary
and interlaboratory attenuation standards, An ideal
RVA possesses the desirable characteristics of a variable
attenuation standard. Among these characteristics are
broad-band performance, low residual loss, negligible
phase variations with changes in attenuation, and elec-
trical performance that can be predicted by a mathe-
matical law. I t is well known that, in the idealized case,
an RVA will obey the COS2 0 law. However, in practice,
there are several major types of RVA errors that cause
deviations from this mathematical law. These are as
follows :
1)
2)
3)
4)
5)
vane angle readout error, which includes errors
due to initial center vane misalignment, gear drive
imperfections, and dial scale inaccuracies;
error due to mutual misalignment of the stator
vanes;
transmission error, which is also referred to as the
error due to insufficient attenuation of the vane in
the rotor;
error due to internal reflections;
error due to external leakage from rotary joints.
lVIost of these error types have been investigated by a
number of authors [1 ]– [7 ]. Other sources of errors are
vane warpage, perturbations of the TEII mode by the
Manuscript received September 24, 1970; revised April 29, 1971.This paper prese~ts the results of on: ph?se of ~esearch earned outat the Jet Propulsion Laboratory, Cahforma Institute of Technology,and sponsored by NASA under Contract NAS 7-100.
The authors are with the Jet Propulsion Laboratory, CaliforniaInstitute of Technology, Pasadena, Calif.
center vane, and eccentricity of the center vane. These
latter error sources have not been fully analyzed but,
with the exception of vane warpage, are presently be-
lieved to produce minor types of errors.
At the Jet Propulsion Laboratory it has been rec-
ognized for several years that, for purposes of antenna
gain and noise temperature calibrations, it is desirable
to incorporate a precision RVA in the receiving system.
The RVA would enable power ratio measurements to be
made by RF substitution methods and therefore would
reduce the present requirements for amplifiers with a
high degree of linearity over a large dynamic range.
The “front end” of the deep space communication an-
tenna systems operating at 2.3 GHz utilizes WR 430
waveguide components that are assembled inside a
Cassegrainian cone housing [8]. Due to the need to keep
the waveguide losses to a minimum, the installation of a
conventional WR 430 RVA (4 or 5 ft in length) was not
considered practical. The requirements for a shorter unit
promoted the development of the compact RVA.
One method of achieving a compact RVA size is to
physically shorten the lengths of the transition and rotor
sections. Shortening the transition secticms should not
noticeably affect RVA performance if the transitions
are well matched. A shortening of the rotor section, how-
ever, generally results in 1) a corresponding reduction in
the useful dynamic attenuation range, 2) an increase in
phase-shift variation as a function of vane angle setting,
and 3) an increase in frequency sensitivity of attenua-
tion and phase-shift characteristics at the higher vane
angle settings.
Such a compact device, therefore, would not be useful
in a swept frequency microwave calibration system
where flat frequency responses of amplitude and phase
characteristics are important. However, a type of sys-
tem where a compact RVA can be useful k a deep space
communication antenna system which operates at spec-
ified fixed frequencies. In the calibrations of the operat-
ing noise temperatures of a low-noise antenna system
by the Y-factor method [9], the accurate dynamic
range of the attenuator does not have to exceed 20 dB
and the relative phase shift does not have to be con-
stant with attenuation setting or with frequency.
The most serious result of shortening thle rotor section
can be the increased effect of the transmission error
signal if it is not properly treated. Transmission error
occurs because the familiar COS28 law assumes complete
attenuation of the E-field component that is tangential
to the rotor resistance card. In this paper, a modified
law that corrects for the effect of the transmission error
signal is derived from basic considerations, The present
844 1SSSTRANSACTIONSON MICROWAVSTHEORYAND TSCPINIQIJE$,NOVSMSSR1971
treatment is similar to that of James [3], but differs in
that the transmission error signal effect is no longer as-
sumed to be of unknown magnitude or phase. Since the
modified law does not require the transmission error
signal to be zero, the attenuator is not required to be
physically long. Therefore, it becomes practical to de-
velop compact RVAS with short rotor sections. The
same modified law can also be used to extend the useful
dynamic attenuation range of high-precision conven-
tional RVAS.
Section II of this paper presents a derivation of the
modified law. Section I I I gives a description of a com-
pact RVA that was fabricated and tested to verify the
modified law. Experimental results and a discussion of
errors are given in Sections IV and V, respectively.
II. THEORY
An RVA consists of three sections of waveguide
mounted in tandem. Across the center of each wave-
guide section is a thin dielectric card that has been de-
posited with 10SSY resistive films. The two end sections,
referred to as stators, are usually rectangular-to-circular
waveguide transitions. The center section, referred to as
the rotor, is a circular waveguide that is free to rotate
between the two stator end sections.
The rectangular waveguide TE1O mode is launched
at the input stator to establish a vertical electric field
~. at the input to the rotor as shown in Fig. 1. This is
decomposed into electric field vectors ZO cos 8 and ~0
sin 6. These two components propagate through the
rotor section of length 1. Defining -y. and ~~ to be the
propagation constants for the electric field vectors nor-
mal and tangential, respectively, to the rotor card, the
vertical component of the electric field at the output of
the rotor can be expressed as
7?U(0) = I?o(e-@ cosz 0 + e–~’Z sin~ 0). (1)
Only the vertical component is considered because the
horizontal component will be attenuated by the output
stator card.
The electrical properties of an RVA that are generally
of interest are incremental attenuation and incremental
phase change. Incremental attenuation is defined as the
change in attenuation of the output wave that results
from rotating the center vane from the 0° setting to the
angle O [10]. Incremental phase change shall be sim-
ilarly defined in this article as the change in phase of the
output wave that results from rotating the center vane
from the 0° setting to angle 0. By definition, and from
(1), the expressions for incremental attenuation and
incremental phase change are
E.(O) ‘~d~ = -– 10 log10 —
EV(0)
IFig. 1. Rotary vane attenuator voltage vectors
at the input to the rotor.
——
where
and
a
( — e–”z sin @ sin2 etan–l
)(3)
cos2 0 + e–aZ cos /31 sin2 0
cY+j(3=yt-yn (4)
cliff erence between the attenuation con-
stants of the tangential and normal elec-
tric field components in the rotor, nepers
per unit length;
difference between the phase shift con-
stants of the tangential and normal elec-
tric field components in the rotor, radians
per unit length;
phase angles of EV(6) and E“(O), respec-
tively, radians.
It is now convenient to introduce two new parameters
that can be experimentally evaluated. These are
& = 1010g~~t?2a’
C$=-fil.
Substitutions into (2) and (3), respectively, result in
modified attenuation law
z4dB = — 10 ]Oglo [COS4 6 + 10–LdB/20
(5)
(6)
the
(7).— 10 Ioglo I COS20 + e–(~+i~)z sin2012 (2) .(2 cos@COS2Osin’0) + 10-~’B/’O sin’0]
OTOSl$lANO STELZRI~D: ROTARYVANE ATTENUATOR 845
and the incremental phase change relationship
[
10–LdB/20 sin @ sinz OA+ = tan–l
1(8)
COS26 + io–LdB/20 cos ~ sin2 6 d
Note that when O= 90° is substituted in (7) and (8),
A dB becomes .&j and A* becomes ~. Therefore, these
two parameters can be experimentally determined by
measuring the incremental attenuation and incremental
phase change when the vane angle is set at 90°. Since the
values of LdB and @ will generally vary with frequency,
the incremental attenuation and phase change relation-
ships given by (7) and (8) will also be functions of fre-
quency. Although (7) and (8) were derived in terms of
the wave at the rotor output, the same equations also
apply to the total attenuator since only incremental
values are of interest. It is assumed that the addition of
the output stator section does not introduce mismatch
or misalignment errors.
It is of interest to examine some special cases of the
modified attenuation law. Note that when LdB ap-
proaches infinity, (7) will reduce to the familiar unmod-
ified law. For cases of finite LdB, analysis of (7) reveals
that, when cos @ < 10–LdB/20, the incremental attenua-
tion will become a maximum at a vane angle setting less
than 90° and have a maximum value greater than Lm.
The following relationships apply for cos @ < 10–~dB/20
(~dB)rnax = ~dB 10=&n = LdB
(L–2dZcos4+l+ 10 logl(l
L sin’4 )(9)
where
L = 10~dB/10 (lo)
‘i
l–dzcosrp6’M = COS–l
L–2~~cos4+l”(11)
If cos @ z 10–LdB/20, the maximum incremental attenua-
tion will always be equal to Lm and will occur at 9 = 90°.
For most RVAS, there will be some deviations be-
tween the indicated and true vane angle due to bore-
sight and other readout errors. The true vane angle can
be expressed as
6’ = & + Cil + a2(eI) (12)
where
& indicated vane angle;
al boresight error (it is the angular misalignment
of the vane in the rotor with respect to the vanes
in the stators when&= 0°;
a7.(61) angle runout error calibrated relative to 61= 0°
setting (it is a function of Or and is due to gearing
errors, bearing runout, eccentricities, etc.).
The vane angle errors al and ~2(&) should be calibrated
to ensure that the RVA follows the law given by (7).
Fig. 2. Compact RVA shown with interchangeable transitions.
Fig, 3. Compact and conventional WR 112 rotary vane attenuators,
With proper mechanical design and use of high-pre-
cision components, the angular errors al and c2Z(01) can
often be made negligibly small.
III. DESCRIPTION OF A TEST
MODEL COMPACT RVA
The test model compact RVA may be seen in Fig. 2.
A pair of stepped transitions, shown installed on the
attenuator, can be interchanged with the other pair of
tapered transitions shown to the left anc[ right of the
attenuator. The attenuator was tested in both the
stepped and tapered transition configurations in order
to determine if any differences would result from use of
shortened transitions as well as a shortened rotor
section.
A comparison of the physical length of the compact
RVA and a conventional WR 112 RVA may be seen in
Fig. 3. (Both attenuators were fabricated by the Mea-
surement Specialties Laboratory of Van Nuys, Calif. )
The rotor length of the compact attenuator is approxi-
mately 3.3 in as compared to a rotor length of about
10.9 in for the conventional attenuator. When the
stepped transitions are installed on the compact attenu-
ator, the overall length is 8.1 in as compared to an over-
all length of 21.6 in for the conventional attenuator.
The compact RVA is fabricated to have a very precise
vane angle readout; the resolution of the readout of the
vane angle position is O.OOO1° and backlash appears to
be less than O.OO1°.
The rotor section of the compact RVA is WC 125
waveguide and contains a vane made from 0.003 -in-
thick mica sheet having a thin layer of metallized resis-
tive film. The resistive film, which has a resistivity of
846
,.
INPUT SIDETRANSITION
IEEE TRANSACTTONS ON MICROWAVE THEORY AND TECHNIQUES, NOVSMSER 1971
9 !
Fig. 4. Rotary vane attenuator represented as the cascade of three multiports. (Numbers refer to measurement portswhile arrows refer to polarization directions.)
90–0+5 Q/square, has been deposited on the mica sheet
in an inverted taper pattern so as to minimize reflec-
tions.
IV. EXPERIMENTAL RESULTS
The experimental evaluation of the compact RVA
consisted mainly of calibrating reflection coefficients,
boresight error, incremental attenuations, and incre-
mental phase change characteristics. The residual loss
of the compact RVA in either the tapered or stepped
transition configuration was measured to be 0.1 dB at
the test frequency of 8448 MHz.
A. Reflection Coejicient
To facilitate the study of internal mismatch errors,
measurements were made of the reflection coefficients
of the individual transitions and rotor secticm. Reflec-
tion coefficients were measured through the use of
WR 112 and WC 125 reflectometer systems tuned at
8448 MHz. The WC 125 reflectometer system was made
to respond only to a single polarization component by
causing the reflected wave of the orthogonal component
to be absorbed in a matched resistive card,
Table I gives a summary of voltage reflection coeffi-
cients measured at various ports of the transitions and
rotor section. As indicated in Fig. 4, an individual port
is identified by a number and is defined for an electric
field that is linearly polarized in the direction of the
arrow. The general symbol S~i denotes the complex
voltage reflection coefficient as seen looking into port i
when all other ports are terminated in nonreflecting
loads. Using a coordinate transformation method similar
to that given in [11], the rotor reflection coefficient
relationships, for the unprimed ports in terms of the
primed ports, are derived as
SS6 = S5,51 cos2 $ + Sb, ~, sin~ $ (13)
S77 = S77V Cosz O + S8t~t sinz 0. (14)
From (13) it can be seen that S~~, and Sb,B, can be deter-
mined by measuring the reflection coefficient at port 5
TABLE I
MEASURED 8448 MHz REFLECTION COEFFICIENTS OFCOMPACT RVA COMPONENTS.
Descriptionof Component
WR 112-t. -WC 125 taperedtransition m inputside of attenuator
WR 1 lZ. to. WC 125 taperedtransition .n outputside .af attematm
WR 112- to-WC 125 steppedtr.nsitmn .n inpntside of attwmator
WR 112. to. WC 125 steppedt=ans,ti.n .n outputside of attenuator
WC 125 rotor section
VO1tage Reflection C.effic lent
Syrnbc.la
‘11
533
544
SZ2
’99
‘%0, 10
%1
S33
544
S22
’99
Slo, 10
‘5,5<
%6$
s ,,, <
S8E8,
Ma@tude
O. 0063
0.0057
0.0102
0.0082
0.0077
0,0101
0.0335
0.0342
0.0063
0.0302
0.0307
0.0014
0.0004
0.0447
0.0045
0.0490
Phase,deg
19.7
-73.5
137.0
18. z
-29.0
156.0
135.1
.87.0
86.8
141.4
-88.5
-173.0
148.1
132.5
138.8
126.6
‘For c.mflgnr.tmn of measurement port t c.rrespmdmg t. S,,, refer mFlg 4.
when 6= O and 90°, respectively. In a similar manner,
S7, ~, and SS ~, can be measured at port 7. The experi-
mentally determined values are given in Table 1. At
other vane angle settings, the measured reflection co-
efficient magnitudes of S65 and S11 agreed with the
values predicted by (13) and (14) to within + 0.001.
The values in Table I were obtained from direct
measurement and are useful for analysis of internal
reflections. When only the overall RVA reflection coeffi-
cient characteristics are known, additional insight into
internal reflections can be obtained from use of a method
described by Helm et al. [12]. The reflection coefficient
characteristic curves of the overall compact RVA and a
conventional RVA are shown in Fig. 5 for comparison
purposes.
847OTOSHI AND STELZRIED : ROTARY VANE ATTENUATOR
0.070 [ 1 I 1 I I I I
(o) TAPERED TRANSITION CONFIGURATION0.060
1 ~Isll[0.050 D--D IS221
~ Islll
0.040G-a IS*21
s 0.030~z
:0.020‘1
COMPACT RVA 1
~ae
CONVENTIONALRVA
R’,n-
,n’
/n’
,ti
/u’
/d
2=
Q 0.010t
g-o-++ .e.Q-~+.&-@-o-+u<)
ozoEu 0.C605.%Lll 0.050
$ <5
$? 0.040
0.030
0.020
0.010
0.
I I I I I I I 1
(b) STEPPED TRANSITION CONFIGURATION
‘Q
‘Q
t I I I 1 t I I10 20 30 40536070S09
1
81, deg
Fig.5. Compact RVAreflection coefficient versus 81 setting.
B. Foresight Error
Boresight error is the misalignment angle term al
defined in (12). A simple procedure for calibrating this
error for conventional RVAS has been described by
Larson [4]. His method is equivalent to substituting an
experimentally measured value of attenuation into an
expression for al derived from the COS2O attenuation law.
The final calibrated al value is obtained by averaging
the al values determined from experimental attenuation
data at several vane angle settings, Larson showed that
the average al value results in a good fit between mea-
sured and theoretical attenuation values over a large
range of vane angle settings for a conventional RVA.
The procedure used to calibrate al of the compact
RVA is identical to the one described for conventional
RVAS except that measured attenuation values are sub-
stituted into a more general al expression derived from
the modified law rather than from the COS2 6’ law. This
general al expression is given in Appendix 1. Due to the
fact that attenuations of a compact RVA deviate sig-
nificantly from the COS2O law even at vane angle settings
as low as 20°, the use of the more general expression is
recommended for accurate calibration of al. A beneficial
outcome of the use of the described calibration proce-
dure is that, if the stator vanes were misaligned with
respect to each other, the effect of this misalignment
would tend to reduce to a type B [6] error which is gen-
erally negligible. This result is also discussed in Ap-
pendix 1.
Since al is a mechanical misalignment angle, its value
can be determined from RF calibrations at ons fre-
quency if internal reflection errors are small. Using 8448
MHz calibrated values of .L~~ and @ and measured at-
tenuation values in the general cu expression (Appendix
I), average values equal to (0.0064 f 10.001 8s1)0 and
(– 0.178 t 0.004si)0 were calibrated for the compact
attenuator in the tapered and stepped transition con-
figurations, respectively. The symbol S? denotes the
calculated standard error based on the number of mea-
surements. The average al value for each configuration
was based on measured attenuations at 27 different vane
angle settings (between 19 and 80°). Thle differences of
the al values for the two transition configurations are
believed to be due mainly to differences in the mechani-
cal alignments of the stator vanes.
C. Incremental A tterwation and Incremental Phase
Change
For conventional RVAS, the incremental phase
change characteristics are not usually measured because
phase changes are negligibly small at attenuation set-
tings below 40 dB. Phase changes are negligible because
LdB is usually very large (90 dB or greater) for most
conventional RVAS. For example, when ~dB is at least
90 dB, the maximum incremental phase change as calcu-
lated from (8) will be less than + 0.25° at vane angle
settings below 85°.
Since the value of LdB is not large for compact RVAS,
the incremental phase change will not be negligibly
small (unless the value of @ is fortuitously equal to zero
or an integer multiple of r rad). Therefore, in the verifi-
cation of the modified attenuation law, it was of interest
to calibrate the incremental phase change characteristics
as well as incremental attenuations. Incremental atten-
uations were calibrated at various indicated vane angles
through the use of an ac ratio transformer test set and
measurement technique described in [13]. (Incremental
phase change measurements were made by the Micro-
wave Standards Laboratory, Hughes Aircraft Com-
pany, Culver City, Calif.)
The results of incremental attenuation and phase
measurements at 8448 MHz are given in Tables I I and
II 1, respectively, for the compact RVA in the tapered
and stepped transition configurations. Theoretical
values are also shown for comparison purposes. I t can
be seen that good agreement between theoretical and
measured values was obtained over abcmt a 20-d B at-
tenuation range. The overall accuracies of the incre-
mental attenuation and incremental phase change
measurements are estimated to be better than f (0.0005
+0.001 XAdB) and f 0.5°, respectively. Theoretical
values were computed through the use c,f (7), (8), (12),
and the following experimentally determined parameter
values.
848 IEEE TRANsACTIONS ON MICROWAVE THEoRY AND T13CHNIQUES, NOVEMRER 1971
TAB LE 11
INCREMENTAL ATTENUATION AND INCREMENTAL PHASE CHANGE FORCOMPACT RVA IN TAPERED TRANSITION CONFIGURATION AT 8.448 GHz.
‘I’ deg
2.787
3.937
4.819
5.562
6.142
6.216
8.779
12.248
12.388
15.142
17.451
19.255
19.474
20.000
27.284
32.712
33.109
37.880
40.000
41.964
44, 932
45.550
Incrementalattenuation, dB
Theo-
reticalvalue
0.0202
0.0403
0.0604
0.0805
0.0982
0.1005
0.201
0.392
0.401
0.601
0.802
0,979
1.002
1.058
z. 003
2. 92S
3.003
4.004
4.506
5.005
5.824
6.006
Measuredminus
theoreticalvalue
-0.0001
-0.0005
-0.0008
-0.0011
.0. 0014
-0.0013
-0.002
-0.001
-0.001
-0.001
0.000
0.001
0.001
0.001
0.000
-0.003
-0.002
-0,001
0.001
0, 002
0.002
0.001
2ncrem,ental phasechange, deg
Theo-
reticalvalue
-0.2
-1.0
Measuredminus
theoreticalvalue
-0.1
-0.1
81, deg
48.752
51.646
54.286
55.782
56.710
59.9.21
60.000
61.028
64.779
68.089
71.051
71.565
73.749
76.259
78.677
80.000
81.146
84.019
85.000
86.012
88.497
89.994
Incrementalattenuatlcm, dB
Theo-
reticalvalue
7.006
8.007
9.008
9.615
10.008
11.468
11.506
12.010
14.012
16.014
18.016
18.384
20.019
22.021
24.025
25.114
26.027
28.030
28.569
29.029
29.714
29. 825a
Measuredminus
theoreticalvalue
0.002
0.004
-0.002
-0.004
-0.005
-0.002
-0.003
-0.003
-0.008
-0.003
0.002
0.003
-0.007
-0.006
0.009
0.013
0.013
0.003
0.000
-0.003
-0.003
—
Incremental phasechange,. deg
Theo.reticalvalue
-4.0
-25.9
-41.6
-50. 7a
Measuredminus
theoreticalvalue
-0.1
0, 0
-0.2
—
Tapered Transition Configuration:
Lm = 29.825 dB
@ = – 50.?0
al = + 0.0064°.
Stepped Transition Con.guration:
Ld, = 29.800 dB
@ = – 50.1”
al = — 0.178°.
The runout error term az(Or) in (12) was assumed to be
zero at all vane angle settings.
As will be discussed further, the small differences in
the measured values of LdB and @ given above for the
two transition configurations resulted from experimen-
tal procedure. Since LdB and ~ are defined to be param-
al%ese are measured values used in the theoretical (7) and (8).
eters of the rotor section only, their values should be
calibrated with the transitions removed. However, for
convenience, calibrations were performed on the overall
RVA configuration. The values of incremental attenua-
tion and phase change (measured when rotating the
center vane from the 0° to 90° setting) were assumed to
be equal to L~, and @, respectively. This experimental
procedure resulted in measured values of&~ and 4 that
were dependent on the mismatch interactions between
the rotor and transition sections. It may be seen from
Table I that the reflection coefficients of the stepped and
tapered transitions are significantly different.
Although the described experimental procedure
causes small errors to occur in the measured values of
&B and @, it is generally more convenient to perform
calibrations in rectangular waveguide rather than in
circular waveguide. It can be shown from an error
analysis study that, in general, the measurements of ~d~
and @ do not have to be made to a high degree of ac-
OTOSHI AND STELZRIED: ROTARY VANE ATTENUATOR
TAB LE III
INCREMENTAL ATTENUATION AND INCREMENTAL PHASE CHANGE FORCOMPACT RVA IN STEPPED TRANSITION CONFIGURATION AT 8.448 GHz.
81, deg
2.787
3.937
4.819
5.562
6.142
6.216
8.779
12.248
12. 38I3
15.142
17.451
19.255
19.474
20.000
27.284
32.712
33.109
37.880
40.000
41.964
44.932
45.550
Incrementalattenuation, dB
Theo-
reticalvalue
O. 0176
0.0366
0.0559
0.0752
0.0923
0.0946
0.192
0.380
0.389
0.586
0.784
0.960
0.982
1.038
1.974
2.892
2.967
3.961
4.459
4.954
5.768
5.948
Measuredminue
theoreticalvalue
0.0005
0.0009
0.0011
0.0010
0.0011
0.0006
0.002
0.002
0.001
0.000
-0.001
0.002
0.002
0.003
0.000
-0.003
-0.003
0.000
0.002
0.004
0.004
0.006
Incremental phase
change, deg
Theo-
reticalvalue
-0.2
-1.0
Measuredminus
theoreticalvalue
-0.2
-0.5
f+, deg
48.752
51.646
54.286
55.782
56.710
59.921
60.000 ‘
61.028
64.779
68.089
71.051
71.565
73.749
76.259
78.677
80.000
81.146
84.019
85.000
86.012
88.497
90.000
90.18
Incrementalattenuation, dB
Theo-
reticalvalue
6.942
7.936
8.930
9.533
9.923
11.372
11.410
11.910
13.896
15.882
17.868
18.233
19.855
21.844
23.840
24.930
25.848
27.883
28.441
28.922
29.659
29.798
29. 800=
Measuredminus
thee.reticalvalue
-0.003
0.009
0.005
0.001
0.004
0.007
0.009
0.005
-0.004
-0.003
-0.004
-0.004
-0.020
-0.034
-0.037
-0.043
-0.052
-0.073
-0.076
-0.075
-0.041
-0.009
—
Incremental phanechange, deg
Theo-reticalvalue
-4.0
-25.1
-40.6
-50. la
Measuredminus
theoreticalvalue
-0.6
-1.2
-0.9
—
849
curacy if the useful dynamic attenuation range of the
RVA is restricted to approximately 2/3 the value of LdB.
D. Broad-Band Frequency Response Data
Incremental attenuation and phase characteristics of
the test model compact RVA over the frequency range
8.0 to 10.0 GHz were measured by means of a computer-
controlled Hewlett-Packard network analyzer system
operated in a phase-locked mode [14]. In this system,
the major systematic errors (such as those due to mis-
match and imperfect couplers) are calibrated so that
corrections can be applied to the measurement data by
a digital computer. (The calibration work was per-
formed by the Computer Metrics facility, Palo Alto,
CaIif.)
Fig. 6 shows the measured frequency responses of LdB
and @ of the compact RVA in the tapered transition
aThese are measured values used in the theoretical (7) and (8).
confkuration. From the accuracy m-aphs for the auto-
mati~ network analyzer [14], it- is- es~imated that the
LdB and @ data are accurate to within ,+ 0.10 dB and
~ 0.5°, respectively. The variation of @ vvith frequency
as indicated in Fig. 6 was greater than anticipated, A
separate experimental study [15 ] showed that the main
cause of the large frequency variation was the resistive
film on the center vane and not the dielectric (mica)
material. However, the dependence of f r{equency sensi-
tivity on resistivity tolerances is not clearly understood.
Later tests made on another $10-,+5-fl rotor card showed
that the total variation over the same frequency range
was a fadOr Of 2 leSS fOr &B and a factOr Of s leSS
for 4.
lVhen calibrated values of LdB and ~ and al= 0.0064°
were applied to the modified theoretical law at each test
frequency (50 MHz steps between 8.0 to 10.0 GHz), the
850 IEEE TRANSACTIONS ON MLCROWAVE THSORY AND TECHNIQUES, NOVEMBER 1971
I I I I I
4
2
-2% 10~.
oz.n%6n
;.
4
2
10-3
-101 I I I
(b) FREQuENCY RESPONSE OF+-15 –
-20 –
-25 –
U -30 –
8z -35 –
EF ~o _.
:$. -45 –
-50 –
-55 –
-60( /
/’///
//,/
I [ I I5 10 15 20 25
FREQUENCY, GHz THEORETICAL ATTENUATION, dB
Fig. 7. Standard error curves for compact RVA.
additional requirement for obtaining broad-band per-
formance of the compact RVA is to calibrate the fre-
quency responses of&B and ~.
V. DISCUSSION OF ERRORS
Fig. 6. Measured frequency response of compact RVAin the tapered transition configuration.
TAB LE IV
THEORETICAL AND MEASURED ATTENUATIONS FOR COMPACT RVAIN TAPERED TRANSITION CONFIGURATION OVER FREQUENCY
RANGE 8.o TO 10.0 GHz.
Theoretical IncrementalAttenbati. ns ,a dB
81.deg
10
20
30
40
50
60
70
80
90
Meamred Minus TheoreticalValues,b dB
8.oGIiz
8.0CR.
-0.01
-0.01
-0.01
0.01
0.01
0.02
0.05
-0.01
—
Error analysis equations for the compact RVA are
derived in Appendix II. Fig. 7 shows error contributions
from various sources of random type errors for the test
model compact RVA. It can be seen that for incremental
attenuations below 10 dB, the principal contributor is
the vane angle readout error. As the incremental attenu-
ation approaches the maximum value, the principal
contributor is the uncertainty in the value of Lm.
The standard error curves in Fig. 7 were derived from
random error equations given in Appendix I I and the
following input parameter values:
10.0GM.
8.5GHz
9.0GHz
9.5GH z
10.0GHz
0,00
0.01
0.00
0.01
0.03
0.03
-0.01
-0. 0.?
O. 262
1.061
2.449
4.522
7.458
11.565
17.379
25.038
28.93
0.261
1.058
2.442
4.508
7.432
11.524
17.354
25.581
31.39
0.263
1.067
2.464
4.557
7.529
11.730
17.872
27.517
38.04
0.00
-0.01
-0.01
-0.01
0.00
0.02
0.02
0.00
-0.02
-0.02
-0.02
0.00
0.00
-0.02
-0.02
0.00
-0.02
-0.02
-0.01
0.00
0.01
-0.01
0.00
-0.04
‘The. ret,cal valuee shown at spot frequencies t. illustrate frequencysensitivity.
LdB = (29.83 i 0.04uj)dB
q = (–50.7 + o.2cr,)0bMeasured values from automatic network analyzer system were given t.two decimaL places.
al = (0.0064 ~ 0.0020-j)0
a2(er) = (0.00 + o.015@)0agreement between theoretical and experimental values
was typically as good as shown in Table IV. The results
appear to indicate that the compact RVA will obey the
modified law over a broad band of frequencies. The where uoI is the standard error of 01. The values of UZ,
OTOSm AND 8TELZRIETJ: ROTARYVANE ATTSNLTATOR
I I I I I
8448 h!tiz CALIBRATION DATA #
● MEASURED DEVIATION, STEPPEDTRANSITION CONFIGURATION
O MEASURED DEVIATION, TAPERED ●
TRANSITION CONFIGURATION●
— THEORETICAL STANDARD ERROR● ,
●✏
/
❑ 0
● ❑
•1●
❑
❑
/
❑ ’@
● 00
●la
I I I I Io 5 10 15 20 25
❑ C
THEORETICAL ATTENUATION, dB
Fig. 8. Plot of measured deviations from theoretical attenuations.
which denotes the standard error, were based on calcu-
lated standard errors or best estimates. Although the
above input parameters are applicable to the compact
RVA in the tapered transition configuration, no signifi-
cant differences in the plotted error curves were found
when these input parameter values were replaced by
those of the stepped transition configuration.
The standard error curve for A dB and absolute values
of the measured deviations from theoretical attenua-
tions at 8448 MHz (Tables II and III) are shown in
Fig. 8. It can be seen that the measured deviations for
the attenuator in the tapered transition configuration
tend to fall under the standard error curve. In the case
of the stepped transition configuration, however, many
of the measured deviation data points are above the
standard error curve. The larger deviations in the case
of the stepped transition configuration are attributed to
increased contributions from systematic errors. Large
systematic errors can result from increased interactions
between the rotor and transition fields due to junction
discontinuity effectsl and internal reflections.
1 At the j unction of the rotor and the stepped transition, the wave-
guide cross section of the stepped transition k somewhat octagonal
rather than circular.
851
An error study indicates that, in the absence of junc-
tion discontinuity effects, the main effect of internal
reflections would be to cause an error to occur in the
calibration of the boresight error angle GUIfor the com-
pact RVA. The analysis of the error due to internal
reflections is presented in Appendix II. It should be
pointed out that the calibration of al can also be affected
by the combined effects of internal reflections, stator
vane misalignment, and rotor vane waqpage.
It has
valid for
VI. CONCLUSIONS
been demonstrated that the modified law is
compact RVAS. When the transitions on the
attenuator were reasonably well matched (VSWRS
E1 .02), the agreement between theoretical and mea-
sured values at 8448 MHz was typically + (0.001
+0.0003 XA dB) over a 30-dB dynamic range. The agree-
ment was degraded to ~ (0.001 +0.001 XA dB) over a
20-dB dynamic range when the stepped transitions
having VSWRS of 1.06 were used. Although these types
of agreement were verified only at a single test fre-
quency, they are representative of those obtainable at
other frequencies if calibrations are performed with a
high-precision insertion loss test set.
The validity of the modified law over a broad band of
frequencies was essentially verified by network analyzer
measurements. Although the values of the parameters
LdB and@ will generally be frequency sensitive and will
vary from unit to unit, they can be very accurately and
economically calibrated over the entire frequency range
by means of an automatic network analyzer. The values
of LdB for a compact RVA will typically be 30 or 40 dB
and therefore be within the accurate measurement range
of the network analyzer. Once the broad-band responses
of LdE and ~ are measured, the data can be used in the
modified attenuation law. With the availability of high-
speed digital computers and programmable desk calcu-
lators, specialized attenuation tables at many frequen-
cies can be supplied for each unit at low cost and with
little additional effort.
The main advantage of the compact RVA is its
reduced size and low residual loss. The disadvantages of
the compact RVA are 1) a reduction in the total dy-
namic attenuation range, 2) the phase-shift variations
that occur as a function of attenuation setting, and 3)
frequency sensitivity. The compact RVA is not intended
to replace the high-precision laboratory-type unit which
offers a large dynamic attenuation range and essentially
constant incremental attenuations and phase change
characteristics with frequency. The compact RVA, how-
ever, would be useful in some systems applications
where a large dynamic attenuation range is not needed
(e.g., operating noise temperature calibrations). Fur-
thermore, a given amount of phase-shift variation can
be tolerable for some types of systems application if the
phase-shift change can be predicted, as is possible in the
case of the compact RVA.
852 IESSTRANSACTIONSON MICROWAVB‘IH50RY AND TSCHNIQUSS,NOV13MB13R1971
APPENDIX 1
ANALYSIS OF BORESIGHT ERROR
CALIBRATION PROCEDURE
A. Bo~esight Error Calibration Equations
From algebraic manipulations of (7) and (12), the
explicit relationship for al is obtained as
al = * arccos v’; — 82 — az(dr) (15)
where
–B+4B2–4ACx=
2A
A = 1 – 10-L’’/20 (2 COS ~)
(15a)
+ 10-L’B”” (15b)
B = 2(10–LdB/20 COS @ – lf)-L’’/lO) (15C)
C = 10–LdB/10 _ lo–AdB/l”. (15d)
The plus sign shown in (15) is chosen if 191has a positive
value and the minus sign is chosen if flI has a negative
value. For (15a) to yield the correct result, it is required
that vane angle settings be restricted to the region
IO I <&.X, where Ore.. has a positive value and is the
vane angle at which maximum attenuation occurs.
The al calibration procedure is to measure the incre-
mental attenuation at a 01 setting and then substitute
the measured value for A dB in (15d) and compute m
from (15). It is assumed that LdB, ~, and cYz(O1) are
known or were previously calibrated. After computing
al values based on measured attenuations at several Or
settings, an average value of al is computed. For best
accuracy, use of data obtained at vane angle settings
close to minimum and maximum attenuation regions
should be avoided.
B. Effect of Stator Vane l.misalignment
The purpose of this analysis is to show that if the
stator vanes were misaligned with respect to each other,
the al calibration procedure will cause the actual rotor
index plane to be established at a plane located approxi-
mately midway between the two stator vanes, By es-
tablishing the rotor index at this plane, a good fit will
result between measured attenuations and the modified
law.
Fig. 9 depicts the geometry of a general stator vane
misalignment case. An arrow at the end of an arc indi-
cates the plane to which the angle is measured with
respect to the reference plane located at the beginning
of the arc. When the arrow points in a counterclockwise
direction, the angle has a positive value in the equations
presented in this analysis. For the general stator vane
misalignment geometry of Fig. 9, the equation for
theoretical attenuations (relative to minimum attenua-
tion) can be derived as
A ‘dB = – 20 ]Oglo
ei+ .
“ Cos “ Cos ‘e’ + “) + Vz “n ‘“ ‘in ’00+ “) ’16)
Fig. 9. Geometry for a general rotorand stator vane misalignment case.
where
ev=eI+&,(eI) +8=8–al+a. (17)
8 angle between the output stator card and the
indicated rotor index plane, rad;
O’ angle of misalignment between stator vanes, rad;
and L was defined previously by (10). Other angles used
in this analysis were previously defined by (12) or can
be defined from Fig. 9.
In the absence of internal reflections, the measured
attenuation values will closely follow those given by
(16). Substitution of (16) for Ad~ in (15d) and compu-
tations of al from use of (15) at many vane angle settings
will result in an average al value of
e’E1E6+ T+;
where the angles are expressed in radians and
( [e’~’
and
(18)
(Cos (#l )sin2 0~— COS2Oi + —
2 4Z L1+
1
(19)Cos + 1
COS2 0< — — cos 20~ — — sin2 0~4Z L,
(20)
The derivation of (19) is involved and cannot be
discussed adequately here. Details of the derivation can
be found elsewhere [16]. The approximate formula
OTOSHI AND STELZRIED : ROTARY VANE ATTENUATOR
given by (18) k useful for showing the relationship be-
tween 0’ and the calibrated ctI value. For most compact
RVA cases likely to be encountered in practice, the
accuracy of the approximate formula for El will typically
be better than 0.001 percent. The approximate formula
becomes inaccurate when vane angle settings approach
e = O, T/2, and fl~, which was defined by (11).
From the geometry of Fig. 9 and substitution of (18)
we obtain
e’Cto=e’+a-ffl =--;.
2(21)
The last expression shows that the new rotor index
plane, established by the boresight error calibration
procedure, will be located approximately midway be-
tween the two stator vanes. If the rotor index were lo-
cated exactly midway between the stator vanes, the
associated attenuation error would be called a type B
error [6] whose magnitude is very small when # is small.
APPENDIX 11
ERROR ANALYSIS
A. Random Errors
For analysis of the accuracy of calibration results it is
usually necessary to know not only systematic error, but
also the individual random error contributions. These
random errors include 1) the random instability of the
measurement system and calibration procedure used,
2) the random instability of the device being calibrated,
and 3) the random error associated with operator per-
formance. In stating magnitudes of random errors, it is
convenient to use the standard error (defined as stan-
dard deviation of the mean value) as a measure of
dispersion.
For the general case, let x be the error source and u.
be the standard error of x. Then the standard
AdB due to CTZ iS
dAdp,rTAdB/x = Uz — .
dx
The individual standard error contributions of
error of
(22)
AdB are
/uAdB d standard error of .4 cIB due to the standard
error of O, decibels;
/uAdB LdB standard error of A dB due to the standard
error of L~B, decibels;
/uAdB 0 standard error of A dB due to the standard
error of 0, decibels.
Application of (22) to the modified law given by (7)
results in
/ r ~$$I (10 log,, e)lo-LdB’20&AdB 4 = —180
.(2 sin @ COS20 sin’0) loA”B1’O I (23)
/~AdB .LdB = aLdB x I(lo-LdB20cos@COS20 sin2 0
+ l&LdBj10 sin4 o)l@dB/10 ] (2A)
853
/fJAdB 8 = ---0 ff~ I (10 loglo e) (4 sin 0 cos 6)
. [(~ - ~@@20 cos ($) (,0S2 @
_ (~@LdB/lo – l@ LdB/20 co, ~)
. sinz O]loAdBi10 (25)
where
u+ standard error of O, degrees;
a~dB standard error of LdB, decibels;
and from (12)
fJ8 = (U012 + Ualz + ua2 )2 112 (26)
where
U@I standard error of Or, degrees;
(ral standard error of al, degrees;
~a2 standard error of cq (Or), degrees.
Treating the above individual sources of errors as if
they were normally distributed, we can compute the
standard error of .4 dB from [17]
rAdB = [(~AdB/d2 + (UAdB/LdB)2 + (ffAC,B/d)2]1/2. (27)
B. Error Due to Internal Reelections
If the effect of internal reflections is accounted for,
the expression of the incremental attenuation for the
compact RVA can be derived as’
()!&E sin’ o2Ad~ = – 20 loglo cos e + ~7,5,
. 20 loglo I 1 + I? sin’0 ~ (28)
where if I Sg, o,/S7,5, ] ~0.032, and neglecting higher order
terms,
R = (S,6 – SWW)SS3 + (SW,, – S,IV)SW -- (SV,)2SWSW
+ (s,,5?)’ COS20(s44s9,+ S33S,O,1O– s33S39)
‘[l+&Fi[(s’’’’-s)s44)+ (s8)8, – 57)7} )510,10 – (s7,5)2s44510,10Sin2g]. (29)
The last term of (28) is the effect due to mismatched
transitions. For example, using measured values of
(SVV) = 0.995 exp (j39.4°)
(s&&) = 0.032 exp (–jl 1.3°)
and the reflection coefficient data for the compact RVA
in the stepped transition configuration in Table 1, the
effect of the transitions is calculated to be – 0.011 dB
at 0=45° and —0.020dB at (3=90°.
z The derivation of this equation was based on scattering parame:
ter coordinate transformations [1 1 ] and a mu ltiport interconnectionmethod [18].
854 IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, VOL. MTr-19, NO. 11, NOVEMBER 1971
ACKNOWLEDGMENT
The author wishes to thank T. Mukaihata and P.
Roberts of the Hughes Aircraft Company for their
cooperation in making incremental phase change cali-
brations on the compact RVA. The work of R. B, Lyon
of Jet Propulsion Laboratory in calibrating reflection
coefficient phase angles is acknowledged. informative
technical discussions with Dr. R. W. Beatty, Dr. G. F.
Engen, B. J, Kinder, W. Larson, and W. E. Little, all
of the National Bureau of Standards, are also acknowl-
edged and appreciated.
[1]
[2]
[3]
[4]
[5]
[6]
[7]
REFERENCES
B. P. Hand, “Broadband rotary waveguide attenuator, ” Elec-tronics, vol. 27, Jan. 1954, pp. 184-185.P. F. Mariner, “An absolute microwave attenuator, ” Proc.Inst. Elec. Eng., vol. 109, Sept. 1962, pp. 415-419.A. V. James, “A high-accuracy microwave-attenuation stan-dard for use in primary calibration laboratories, ” IRE T’nwzs.Instrum., vol. I-11, Dec. 1962, pp. 285-290.W. Larson, “Analysis of rotation errors of a waveguide rotaryvane attenuator, ” IEEE Trans. Instrurn. Mess., vol. IM- 12,Sept. 1963, pp. 50-55.—, “Gearing errors as related to alignment techniques of therotary-vane attenuator, ” IEEE Trans. Instrum. Meas., vol.IM-14, Sept. 1965, pp. 117-123.— “Analysis of rotationally misaligned stators in the rotary-vane’ attenuator, ” IEEE Trans. Instrusn. Meas., vol. IM-16,Sept. 1967, pp. 225-231.W. E. Little, W. Larson, and B. J, Kinder, “Rotary-vane at-tenuator with an optical readout, ” J. Res. Nat. Bur. Stand.,
[8]
[9]
[10]
[11]
[12]
[13]
[14]
[15]
[16]
[17]
[18]
vol. 75C, Jan.–Mar. 1971, pp. 4148.G. S. Levy, D. A. Bathker, W. Higa, and C. T. Stelzried, “Theultra con;: an ultra-low noise s~ace communication groundradio-frequency system, ” IEEE Trans. Microwave TheoryTech., vol. MTT-16, Sept. 1968, pp. 596-602.C. T. Stelzried, “Operating noise-temperature calibrations oflow-noise receiving systems, ” Microwave J., vol. 14, June 1971,pp. 4148.R. W. Beatty, “Insertion loss concepts, ” PYOC. IEEE, vol. 52,June 1964, pp. 663-671.C. G. Montgomery, R. H. Dicke, and E. M. Purcel!, Principlesof Mzcrowave Czwxiis (Radiation Laboratory Series, VOI. 8).New York: McGraw-Hill, 1948, p. 351.J. D. Helm, D. L. Johnson, and K. S. Champlin, “Reflectionsfrom rotary-vane precision attenuators, ” IEEE Trans. Micro-wave Theory Tech. (Corresm ), vol. MTT- 15, Feb. 1967, DD.
123-124. - ‘ “ ‘. .
C. J. Finnie, D. Schuster, and T. Y. Otoshi, “AC ratio trans-former technique for precision insertion loss measurements, ”~ F“~~lsion Lab., Pasadena, Calif., Tech. Rep. 32-690, Nov.
S. ‘F. Adam, “A new precision automatic microwave measurementsystem, ” IEEE T?ans. Instrum. Meas., vol. IM-17, Dec. 1968,pp. 308-313.T. Y. Otoshi, “Improved RF calibration techniques: a precisioncompact rotary vane attenuator, ” Jet Propulsion Lab., Pasa-dena, Calif., Space Programs Summary 37-64, vol. II, Aug. 31,1970, pp. 67-69.T, Y. Otoshi, “Analvsis of the boresizht error calibration cmo-cedure for compact “rotary vane atte-nuators, ” Jet Propul~ionLab., Pasadena, Calif., Tech. Rep. 32-1526, vol. III, June 15,1971, pp. 126–132.A. Worthing and J. Geff ner, Treatment of Experimental Data.New York: Wiley, 1960, p. 213.Thomas-Alfred Abele, “Uber die Streumatr~x Allgemein Zusam-mengeschalteter Mehrpole, ” J“The scattering matrix of a gen-eral mterconnectlon of multlpoles”), Ad. Etek. Ubert~agung,vol. 14, pt. 6, 1960, pp. 262–268 (Transl, m NASA ReportNASA-CR-1014O4).
A Group Theoretic Investigation of the
Single-Wire Helix
JEFFREY B. KNORR, MEMBER, IEEE, AND PAUL R. McISAAC, MEMBER, IXEE
Abstract—Thk$ paper discusses the way in which symmetrygroups may be utilized in the analysis of periodic microwave struc-
tures. The theory of group representations is introduced, and the
relationship of these representations to the vector electromagnetic
fields which are solutions to the Hehnholtz equation (subject to the
boundary conditions imposed by the microwave structure) is briefly
explained, Also ezplained is the concept of time reversal. Symmetry
analysis involves collecting all of the symmetry operations of a
microwave structure into a group, and then finding the irreducible
representations of that group. Each solution of the Hehnholtz equa-
tion must belong to an irreducible representation of the space group,
and by examining the irreducible representations it is possible to
determine the symmetries and degeneracies of the waves. Symmetry
analysis is employed to describe some of the characteristics of the
Manuscript received October 21, 1970; revised April 19, 1971.J. B. Knorr was with the School of Electrical Engineering, Cornell
University: Ithaca, N. Y. He is now with the Department of Elec-trical Engineering, Naval Postgraduate School, Monterey, Calif.
P. R. McIsaac is with the School of Electrical Engineering,Cornell University, Ithaca, N. Y.
waves of the unsupported wire helix and of the single-wire helix
supported symmetrically by three dielectric rods. In particular, the
conditions for the occurrence of branch crossings on the k-b diagram
are discussed.
I. INTRODUCTION
SYMMETRY analysis has been extensively applied
in chemistry and physics to provide information
concerning the solutions of compIex problems aris-
ing in those fields. Since most microwave structures of
practical interest exhibit some degree of symmetry, it
would appear that the application of symmetry analysis
to microwave theory would also be fruitful. However,
with the exception of the analysis of symmetrical micro-
wave junctions [1 ], [2], symmetry analysis has received
relatively little attention from microwave engineers.
There appear to be several reasons for this neglect of
symmetry analysis. Firstly, the abstract group theory