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SPICE活用入門 (02AUG2013)
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1.SPICEの最適な環境について 2.SPICEの弱点について 3.SPICEの再現性を高める方法について 4.収束エラー改善方法について 5.質疑応答
SPICE活用入門
1 Copyright (C) Bee Technologies Inc. 2013
1.SPICEの最適な環境について
環境
ツール
SPICEモデル
シミュレーション技術
2 Copyright (C) Bee Technologies Inc. 2013
1.SPICEの最適な環境について
ツール
3 Copyright (C) Bee Technologies Inc. 2013
1.SPICEの最適な環境について
SPICEモデル
(1)サプライヤ企業から提供してもらう (2)スパイスモデル配信サイト:スパイス・パークを利用する → http://www.spicepark.info (3)自分で作成する →デバイスモデリング教材の活用 →デバイスモデリングセミナーの活用 →部品モデル作成術(書籍の活用) (4)デバイスモデリングサービスを活用する →半導体部品、受動部品、バッテリー、 センサー、モーター、機構部品等 (5)パラメータベースのシンプルモデルを活用する →シンプルモデル
4 Copyright (C) Bee Technologies Inc. 2013
1.SPICEの最適な環境について
SPICEモデル:スパイスモデル配信サイト:スパイス・パーク
5 Copyright (C) Bee Technologies Inc. 2013
1.SPICEの最適な環境について
シミュレーション技術=回路モデリング
(1)概念設計 概念設計段階の回路方式の検討のテンプレート →コンセプトキット 電子書籍(Kindle,PDF)+デザインキット(PSpice,LTspice) →Kindle版はAMAZONで発売中 →PDF版は、マルツエレックで発売中 (2)詳細設計 詳細設計段階の回路方式の検討のテンプレート →デザインキット お客様の回路図をシミュレーション化 →カスタム・デザインキット
6 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
(1)破壊の概念がない(耐圧の概念がない) →ヒューズのシンプルモデルの活用 (2)DC電源 安全動作領域がない 大電流が流れる →DC電源のシンプルモデルの活用 CVCC電源のシンプルモデルの活用
U1CVCCPS
CC = 5ACV = 5V
1
2
U1DC_POWER_SUPPLY
VOUT = 80VdcIMAX = 160AdcVMAX = 80VdcPOWER = 1600W
7 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
The model accounts for:
• Current Rating
• Fuse Factor
• Internal Resistance
• Normal Melting I2t
Enable the model to simulate fusing time
(blow time) as a function of I2t.
The model can be used for testing the
blow time for the different current
pattern.
A one-shot switch, once fuse is opened it
cannot be closed.
Fig.1 Fusing Time vs. Fusing Current Characteristic
0.001
0.01
0.1
1
10
0.1 1 10 100
Fu
sin
g T
ime
(S
ec
.)Fusing Current (A)
8 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
Irate = the current rating of fuse [A]
FF = Fusing Factor, the ratio of the
minimum fusing current (the current
that fuse start to heat up) to Irate.
(e.g. Irate =400mA and the minimum
fusing current is 620mA then FF =
620m/400m = 1.55)
Rint = internal resistance of fuse
I2t = Normal Melting value [A2, seconds]
• From the fuse specification, the model is characterized by setting parameters Irate, FF,
Rint and I2t.
Model Parameters:
Fig.2 Fuse model with default parameters
IRATE = 400m
FF = 1.55
RINT = 650m
I2T = 0.024
9 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
0.001
0.01
0.1
1
10
0.1 1 10 100
Fu
sin
g T
ime
(S
ec
.)
Fusing Current (A)
Fig.3 Shows the complete setting of fuse model parameters by using data from the
datasheet of CCF1N0.4 provided by KOA Speer Electronics, Inc.
the minimum fusing current
is 620mA, FF = 20m/400m
= 1.55
IRATE = 400m
FF = 1.55
RINT = 650m
I2T = 0.024
10 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
• The simulation result shows the fusing times, tF, (the time that fuse blows) at
the different fuse currents, IF .
tF = 956.677usec. at IF = 5A
tF = 5.9221msec. at IF = 2A
tF = 23.7861msec. at IF = 1A
Simulation Circuit
*Analysis directives:
.TRAN 0 1s 0 100u
.STEP PARAM dc_current LIST 1, 2, 5
*Integration Method: trapezoidal
Simulation Result
11 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
0.001
0.01
0.1
1
10
0.1 1 10 100
Fu
sin
g T
ime
(S
ec
.)
Fusing Current
Measurement
Simulation
Graph shows the comparison result between the simulation result vs. the
measurement data. The fusing current error (average from 0.001-10 sec.) = 4.9%
Comparison Graph
12 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
• The simulation result shows the fusing times, tF, (the time that fuse blows)
for the same peak current but different in current patterns(waveforms).
tF = 59.984msec. for sine wave
tF = 150.041msec. for triangle wave
Simulation Circuit Simulation Result
.TRAN 0 0.2s 0 100u
*Integration Method: trapezoidal
13 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
ヒューズ
0.001
0.01
0.1
1
10
0.1 1 10 100
Fu
sin
g T
ime
(S
ec
.)Fusing Current
Measurement
Simulation
If the most accurate result is required, we could provide the specific model that
optimized for each part number of fuse. The fusing current error (average from 0.001-
10 sec.) will reduce from 4.9% (simplified model) to 0.4% (specific fuse model)
Model of fuse part number CCF10.4, all parameters and
function are already set
Error reduce to 0.4%
Comparison Graph
14 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
DC電源
• This DC Power Supply Simplified SPICE Behavioral Model is for users who
require the model of a DC power supply as a part of their system.
• The model focuses on the power supply’s behavior in their operation area,
which user can input rated voltage, rated power, and maximum output
current.
Rated output voltage
Rated output line (from Rated Power)
Output Voltage [V]
Output Current [A]
Operation Area Maximum output current
15 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
DC電源
POWER Rated power
– e.g. 400W, 800W, 1600W
– Value = <POWER>
VMAX DC maximum output voltage
– e.g. 80V, 320V, 650V
– Value = <VMAX>
IMAX DC maximum output current
– e.g. 40A, 80A, 160A
– Value = <IMAX>
VOUT Output voltage
– 0 ~ VMAX
– Value = <VOUT>
• From the DC power supply specification, the model is characterized by setting
parameters POWER, VMAX, and IMAX, then input VOUT value (from 0 to VMAX).
U1DC_POWER_SUPPLY
VOUT = 80VdcIMAX = 160AdcVMAX = 80VdcPOWER = 1600W
Model Parameters:
16 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
DC電源
I(OUT)
0A 20A 40A 60A 80A 100A 120A 140A 160A 180A 200A
V(OUT)
0V
20V
40V
60V
80V
100V
(160.000,9.990)
(20.000,79.991)
(160.000,9.990)
Rated output voltage
Maximum output current
Rated output line
Rated operation
range
17 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
DC電源
*Analysis directives:
.DC LIN I_ILOAD 0 200 10m
.PROBE V(*) I(*) W(*) D(*) NOISE(*)
DC Sweep: ILOAD 0-200A
0
OUT
OUT
ILOAD
U1DC_POWER_SUPPLY
VOUT = 80VdcIMAX = 160AdcVMAX = 80VdcPOWER = 1600W
18 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
DC電源
Time
0s 10ms
V(OUT)
0V
20V
40V
60V
80V
100V
Parameter VOUT = 40V
60V
80V, and 100V
V(OUT) is limited by the model parameter VMAX (80V)
19 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
CVCC電源
U1CVCCPS
CC = 5ACV = 5V
1
2
CV and CC value set only
CV: Constant Voltage [V]
CC: Constant Current [A]
Default Value:
CV=5V: Constant Voltage [V]
CC=5A: Constant Current [A]
20 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
CVCC電源
I_ILoad
0A 1.0A 2.0A 3.0A 4.0A 5.0A
V(H1:1,H1:2)
0V
1.0V
2.0V
3.0V
4.0V
5.0V
6.0V
7.0V
8.0V
CV=6V
CV=5V
CV=4V
CC=5A I_ILoad
0A 1.0A 3.0A 5.0A 7.0A
V(H1:1,H1:2)
0V
1.0V
2.0V
3.0V
4.0V
5.0V
6.0V
7.0V
8.0V
CC=4A CC=5A
CC=6A
CV (Constant Voltage) CC (Constant Current)
CV=5V
21 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
CVCC電源
[How to set]
.MODEL MPOPS PMOS
+ LEVEL=3 L=1u W=1u TOX=100n
+ VTO=-0.7 KP={22.2222*CC}
RD={(0.37*CV)/CC}
+ RDS=100MEG N=1MEG
Load Regulation
I_ILoad
0A 1.0A 2.0A 3.0A 4.0A 5.0A
V(H1:1,H1:2)
0V
1.0V
2.0V
3.0V
4.0V
5.0V
6.0V
I_ILoad
0A 1.0A 2.0A 3.0A 4.0A 5.0A
V(H1:1,H1:2)
0V
1.0V
2.0V
3.0V
4.0V
5.0V
6.0V
RD={(0.1*CV)/CC}
RD={(0.37*CV)/CC}
Symbol of the CV|CC Power Supply Model
U1CVCCPS
CC = 5ACV = 5V
1
2
22 Copyright (C) Bee Technologies Inc. 2013
2.SPICEの弱点について
CVCC電源
I_ILoad
0A 1.0A 2.0A 3.0A 4.0A 5.0A
V(H1:1,H1:2)
0V
1.0V
2.0V
3.0V
4.0V
5.0V
6.0V
[How to set]
.MODEL MPOPS PMOS
+ LEVEL=3 L=1u W=1u TOX=100n
+ VTO=-0.7 KP={22.2222*CC}
RD={(0.37*CV)/CC}
+ RDS=100MEG N=1MEG
Load Regulation
The parameter RD is deleted
Symbol of the CV|CC Power Supply Model
U1CVCCPS
CC = 5ACV = 5V
1
2
23 Copyright (C) Bee Technologies Inc. 2013
Most electronic ballasts and switching power supplies use a bridge rectifier and a bulk storage capacitor to derive raw dc voltage from the utility ac line, figure above: Vin=100Vac, 50Hz and PO=200W.
24
Vin
AC_IN1
PARAMETERS:
f req = 50Hz
Vin = 100Vac
AC_IN2
Cbulk2000uF
0
bulkDB1
DB2DB3
Diode
DB4
Load
1.414Adc
Iline
Vbulk
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
160ms 164ms 168ms 172ms 176ms 180ms 184ms 188ms 192ms 196ms 200ms
AVG(ABS(W(Vin)))/(RMS(ABS(V(AC_IN1,AC_IN2)))*RMS(ABS(I(Vin))))
0
0.2
0.4
0.6
0.8
1.0
ABS( I(Vin) )
0A
10A
20A
ABS( V(AC_IN1,AC_IN2) ) V(bulk)
0V
100V
200V
SEL>>
The Uncorrected Power Factor rectifying circuit draws current from the ac line when the ac voltage exceeds the capacitor voltage (Vbulk). The current (Iline) is non-sinusoidal. This results in a poor power factor condition where the apparent input power is much higher than the real power, figure above, power factor ratios of 0.5 to 0.7 are common.
25
|VAC, in, 100V| (VPEAK, in=100*2=141.42V) and Vbulk
|Iline|
Power Factor Ratio = Pin, avg./(Vin, rms* Iin, rms)
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Vac, inC1
1uF
C2
200u
ILoad
0.5A
L112
Diode
D2
Q1MOSFET
R7
L21 2
0
0
Rectifiers PFC
TB6819AFG
Controller
Circuit
PARAMETERS:
f req = 50Hz
Vin = 100Vac
The Power Factor Correction (PFC) circuit, as an off-line active preconverter, is designed to draw a sinusoidal current from the AC line that is in phase with input voltage. As a result, the power factor ratio is improved to be near to ideal (1).
The TB6819AFG is a critical conduction mode (CRM) PFC controller IC. The description including equation and constants as a guide to understand its designing process is included in this document.
26
Iline
VDC, OUT
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time*10
100ms 104ms 108ms 112ms 116ms 120ms 124ms 128ms 132ms 136ms 140ms
AVG(ABS(W(Vin))) / (RMS(ABS(V(AC_IN1,AC_IN2)))*RMS(ABS(I(Vin))))
0
0.2
0.4
0.6
0.8
1.0
-I(Vin)
-8.0A
0A
8.0A
SEL>>
1 V(AC_IN1,AC_IN2) 2 V(VOUT)
-160V
0V
160V1
200V
400V
600V2
>>
The poor power factor load is corrected by keeping the ac line current sinusoidal and in phase
with the line voltage. This results with power factor ratio is 0.85.
27
VAC, in, 100V and VDC, OUT, 400V
Iline
Power Factor Ratio = 0.85
*simulation result at tscale = 10
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Load
0.5A
R12
39k
C9
0.1uF
Vin
FREQ = {f req}
VAMPL = {Vin*1.414}
AC_IN1
R4 100
PARAMETERS:
f req = 50
Vin = 100
C6 3300p
AC_IN2
C11u
0
0
R93MEG
R1022k
C5
10nF
C8
47uFIC = 17.9
D5DZ18V
R11360k
R668k
R8100k
MULT
Rtf
C30.47uF
IC = 3.74
L1{L}
12
PARAMETERS:
L = 230u
N = {1/9.6}
N=N2/N1, L2=(N^2)*L1
VCC
V1
R70.11
PO
UT
V2
U1
TB6819AFG
FB
_IN
CO
MP
MU
LT
ISZ
CD
GN
D
PO
UT
VC
C
FB_IN
IS
ZC
D
C78p
R310k
C4
1uF
VOUT
R21.5MEG
R19.53k
C2 200uF
IC = {2.51*1509.53/9.53}
COMP
L2{N*N*L}
1 2
K
K1
COUPLING = 1
K_Linear
L1 = L1
L2 = L2
DB1
Diode
D2
Diode
D3
DiodeD4
DB2DB3
Diode
DB4
Q1MOSFET
R5
10
28
VAC, in=85-265VAC
PO = 200W, VDC, OUT = 400VDC
*Analysis directives: .TRAN 0 20ms 0 100n .OPTIONS ABSTOL= 100n .OPTIONS GMIN= 1.0E-8 .OPTIONS ITL1= 500 .OPTIONS ITL2= 200 .OPTIONS ITL4= 40 .OPTIONS RELTOL= 0.01 .OPTIONS VNTOL= 100u
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
18.00ms 18.25ms 18.50ms 18.75ms 19.00ms 19.25ms 19.50ms 19.75ms 20.00ms
ID(Q1)
-6A
0A
6A
12A
V(Q1:d,Q1:s)
0V
200V
400V
600V
I(D2)
8A
16A
-2A
SEL>>
V(D2:2,D2:1)
0V
200V
400V
600V
Switching Devices VPEAK and IPEAK at Steady State
29
D2 VKA, Peak ≈ 400V at steady state
Total simulation time = 976.83 seconds
D2 IF, Peak ≈ 12A at steady state
Q1 VDS, Peak ≈ 400V at steady state
Q1 ID, Peak ≈ 7.2A at steady state
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Load
0.5A
R12
39k
C9
0.1uF
Vin
FREQ = {f req*tscale}
VAMPL = {Vin*1.414}
AC_IN1
R4 100
PARAMETERS:
f req = 50
Vin = 85
C6 3300p
AC_IN2
C11u
0
0
R93MEG
R1022k
C5
{10n/tscale}
C8
47uFIC = 17.9
D5DZ18V
R11360k
R668k
R8100k
MULT
Rtf
C3{0.47u/tscale}
L1{L}
12
PARAMETERS:
L = 230u
N = {1/9.6}
N=N2/N1, L2=(N^2)*L1
VCC
V1
R70.11
PO
UT
V2
U1
TB6819AFG
FB
_IN
CO
MP
MU
LT
ISZ
CD
GN
D
PO
UT
VC
CFB_IN
ISZ
CD
C78p
R310k
C4
{1u/tscale}
VOUT
R21.5MEG
R19.53k
C2 {200u/tscale}
PARAMETERS:
tscale = 40
COMP
L2{N*N*L}
1 2
K
K1
COUPLING = 1
K_Linear
L1 = L1
L2 = L2
DB1
Diode
D2
Diode
D3
DiodeD4
DB2DB3
Diode
DB4
Q1MOSFET
R5
10
Switching Devices VPEAK and IPEAK at Start Up 30
Vin, min = 85Vac with frequency 50Hz, tscale = 40
Iload = 0.5A as PO=200W at VO=400V
I(D2)
Switching Diode, D2
*Analysis directives: .TRAN 0 10ms 0m 100n .OPTIONS ABSTOL= 100n .OPTIONS GMIN= 1.0E-8 .OPTIONS ITL1= 500 .OPTIONS ITL2= 200 .OPTIONS ITL4= 40 .OPTIONS RELTOL= 0.01 .OPTIONS VNTOL= 100u
ID(Q1)
Switching MOSFET, Q1
Rectifier Diode, DB1-4
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
476us 480us 484us 488us 492us 496us 500us 504us 508us 512us 516us
V(V2)
0V
40V
-I(L1)
0A
5A
10A
V(V1)
0V
250V
500V
V(Q1:g)
10V
20V
SEL>>
Time
0s 0.5ms 1.0ms 1.5ms 2.0ms
V(VOUT)
392V
400V
31
The Simulation Waveform with the defaults models
V(V1)
I (L1)
V(V2)
V(VOUT) without high frequency ripple which is caused by ESR and ESL of the capacitor model.
Gate charge characteristics is not include in the default model.
Total simulation time = 132.41 seconds
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Load
0.5A
R12
39k
Q22SK2611
C9
0.1uF
Vin
FREQ = {f req*tscale}
VAMPL = {Vin*1.414}
AC_IN1
R4 100
PARAMETERS:
f req = 50
Vin = 100
C6 3300p
AC_IN2
C11u
0
0
R93MEG
R1022k
C5
{10n/tscale}
C8
47uFIC = 17.9
D5DZ18V
R11360k
R668k
R8100k
MULT
Rtf
C3{0.47u/tscale}
IC = 3.74
L1{L}
12
PARAMETERS:
L = 230u
N = {1/9.6}
N=N2/N1, L2=(N^2)*L1
VCC
V1
R70.11
PO
UT
V2
U1
TB6819AFG
FB
_IN
CO
MP
MU
LT
ISZ
CD
GN
D
PO
UT
VC
CFB_IN
ISZ
CD
C78p
R310k
C4
{1u/tscale}
VOUT
R21.5MEG
R19.53k
COMP
L2{N*N*L}
1 2
K
K1
COUPLING = 1
K_Linear
L1 = L1
L2 = L2
C2
RJJ-35V221MG5-T20
D2
SCS110AG
DB1
Diode
D3
DiodeD4
PARAMETERS:
tscale = 10
DB2DB3
Diode
DB4
R5
10
Simulation with Models from the SpicePark 32
Capacitor model
MOSFET professional
model
Schottky diode model
Replace some default model with models from SpicePark
*Analysis directives: .TRAN 0 2ms 0 100n .OPTIONS ABSTOL= 100n .OPTIONS GMIN= 1.0E-8 .OPTIONS ITL1= 500 .OPTIONS ITL2= 200 .OPTIONS ITL4= 100 .OPTIONS RELTOL= 0.01 .OPTIONS VNTOL= 100u
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
【参考】インダクタの等価回路の考え方
10-3
100
103
106
109
(Hz)
Impedance vs. Frequency
Inductor model
R1L1
L1
R1
R1L1C1
L1
10-3
100
103
106
109
(Hz)
Impedance vs. Frequency
Inductor model
R1L1 R1L1
L1
R1
L1
R1
R1L1C1
R1L1C1
L1L1
33
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Frequency
1.0KHz 10KHz 100KHz 1.0MHz 10MHz
V(V1:+)/ I(V1)
1.0
10
100
1.0K
10K
100K
(2.1878M,234.735K)
All Rights Reserved Copyright (C) Bee Technologies Inc. 34
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
ラダー・モデル(Rudder Model)
Frequency
100Hz 1.0KHz 10KHz 100KHz 1.0MHz 10MHz 100MHz
V(N01685)/I(V2)
10m
100m
1.0
10
100
1.0K
10K
35
C1
1 2
R1
L2
C2
L1
R2
RS
*$ *PART NUMBER: SF-T5-25-01-PF *MANUFACTURER: TDK *All Rights Reserved Copyright (c) Bee Technologies Inc. 2006 .SUBCKT SF-T5-25-01-PF 1 2 R1 1 N4 2.89441k RS N4 2 37.9262m C1 1 N4 5.81894p L1 1 N3 12.151u L2 N3 N4 24.0673u R2 N3 N4 592.966 C2 N3 N4 2.2969p .ENDS *$
SPICEシミュレーション結果 インピーダンス測定結果(Agilent 4294A)
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
484us 488us 492us 496us 500us 504us 508us 512us 516us 520us 524us
V(V2)
0V
40V
-I(L1)
0A
5A
10A
V(V1)
0V
250V
500V
V(Q2:g)
10V
20V
SEL>>
Time
0s 0.2ms 0.4ms 0.6ms 0.8ms 1.0ms 1.2ms 1.4ms 1.6ms 1.8ms 2.0ms
V(VOUT)
392V
400V
36
V(VOUT) with high frequency ripple which is caused by ESR and ESL of the capacitor model.
Gate charge characteristics is include in the MOSFET Professional model.
V(V1)
I (L1)
V(V2)
Total simulation time = 408.13 seconds
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
37
パワーMOSFETのスパイスモデルについて
MOSFET LEVEL LEVEL=1 Shichman-Hodges Model LEVEL=2 形状に基づいた解析モデル LEVEL=3 半経験則短チャネルモデル LEVEL=4 BSIM Model LEVEL=6 BSIM3 MODEL ・・・・・・・ ・・
MOSFET LEVEL=3 半経験則短チャネルモデルの特徴 (1)2次元的な電位分布によるデバイスの長さ及び幅に対してスレッシュホルド電圧 が敏感に影響を受ける。 (2)ドレインが誘起するBarrier loweringによるドレイン電圧に対してのスレッシュホルド電圧 の考慮。 (3)リニア領域と飽和領域との間での緩やかな変化及びホットエレクトロンの速度 飽和によって若干減少する飽和電圧、飽和電流の考慮。
RB
BulkGate
Cbs
Cgb
RG
Cgd
ROS
Cgs
RD
RS
Cbd
Drain
Source
Idrain
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
38
Time*1ms
0 8n 16n 24n 32n 40n
V(W1:2) V(W201:2)
0V
2V
4V
6V
8V
10V
12V
14V
16V
18V
20V
MOSFET LEVEL=3 MODEL Bee Technologies MODEL(Professional)
ゲートチャージ特性 ミラー容量が固定値のため、ミラー容量を可変にする
電流臨界モード方式PFC制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
39
Condition :
Po = 25[W], 4 Load Analysis Time Domain (Transient) Run to time: 3ms Start saving data after: 1ms Maximum step size: 100n Skip the initial transient bias point calculation (SKIPBP)
.Options RELTOL: 0.01 VNTOL: 1.0u ABSTOL: 1.0n CHGTOL: 0.01p GMIN: 1.0E-12 ITL1: 500 ITL2: 200 ITL4: 10
TEST CONDITION:
C41nF
0
+B15V
+
C18EKMG500ELL222MLP1S
C51nF
0
R1810
0
R192.2k
PARAMETERS:
Po = 25W
Gv = 15.85
RL = 4
f in = 1kHz
C14MMH250K684
R4220
C710uIC = 10
R2
3kR1100k
C10 22uIC = 15
LOAD
{RL}
OUT
C922uIC = 12.85
MUR120RLG
D2
IN
VS
R1310
R3
47k
L17G14N-220-RB
VB
R171
R20
3.3k
0
R218.2k
R8
820
+B
VAA
0
VREF
R6 8.2k
R71.2k
CSD
OCSET
IN-
IC1
IRS2092
VAA
GND
IN-
COMP
CSD
VSS
VREF
OCSET DT
COM
LO
VCC
VS
HO
VB
CSH
VCC
0
DT
VSS 0
COMP
R5
820
-B
HO
R15
10
LO
VR175
-B-15V
0
C210uIC = 7
C810uIC = 7
R1110k
V1
FREQ = {f in}VAMPL = {1.4142*SQRT(Po*RL)/Gv }VOFF = 0
VS
CSH
C13MMC400K104
0
C12MMC250K474
R16
10
C11RPER11H104K2K1A01B
C15RPER11H104K2K1A01B
0
R144.7
MUR120RLGD1
0
R9
4.7k
+ C16EKMG500ELL222MLP1S
C17RPER11H104K2K1A01B
R1210k
C3
RPER11H103K2K1A01B
+C1
EKMG500ELL100ME11DC6AMZ0050J102
FET1IRFIZ24N
FET2IRFIZ24N
Ls1
20nH
1
2
Ls2
20nH
1
2
Ls320nH
1
2
Ls420nH
1
2
Ls520nH
12
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
40
Time
1.0ms 1.5ms 2.0ms 2.5ms 3.0ms
1 AVG(W(LOAD)) -(AVG(W(+B))+AVG(W(-B))) 2 -100*AVG(W(LOAD))/(AVG(W(+B))+AVG(W(-B)))
0W
5W
10W
15W
20W
25W
30W
35W
40W
45W
50W1
>>
0
10
20
30
40
50
60
70
80
90
1002
PSUPPLY [W]
PO [W]
%Efficiency
Specifications : Efficiency Simulation Result
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
+
-
SPEAKERF120A
FET1IRFIZ24N
FET2IRFIZ24N
+
C1EKMG500ELL100ME11D
C6AMZ0050J102C3
RPER11H103K2K1A01B
V1
FREQ = {f in}VAMPL = { 1.4142*VOUT/Gv }VOFF = 0
0
C41nF
+B15V
+
C18EKMG500ELL222MLP1S
C51nF
0
R1810
0
R192.2k
C14MMH250K684
R4220
C710uIC = 10
R23k
R1100k
C10 22uIC = 15
OUT
C922uIC = 12.85
MUR120RLG
D2
VS
IN
R1310
R3
47k
L17G14N-220-RB
VB
R171
0
R20
3.3k
R218.2k
R8
820
+B
VREF
VAA
0
R6 8.2k
R71.2k
CSD
OCSET
IN-
IC1
IRS2092
VAA
GND
IN-
COMP
CSD
VSS
VREF
OCSET DT
COM
LO
VCC
VS
HO
VB
CSH
VCC
0
DT
VSS 0
COMP
HO
R5
820
-B
R15
10
LO
VR175
-B-15V
0
C210uIC = 7
C810uIC = 7
R1110k
CSH
VS
C13MMC400K104
0
C12MMC250K474
R16
10
C11RPER11H104K2K1A01B
C15RPER11H104K2K1A01B
0Ls1
20nH
1
2
Ls2
20nH
1
2
Ls320nH
1
2
Ls420nH
1
2
R144.7
MUR120RLGD1
0
R9
4.7k
+ C16EKMG500ELL222MLP1S
Ls520nH
12
C17RPER11H104K2K1A01B
R1210k
PARAMETERS:VOUT = 2Gv = 15.85f in = 1k
V
V
V
V V
V
41
Time
505.0us 510.0us
V(VS)
-40V
0V
40V
Time
505.0us 510.0us
V(HO)
-40V
0V
40V
Time
505us 510us503us 513us
V(LO)
-20V
0V
Time
0.50ms 0.75ms 1.00ms 1.25ms
V(IN)
0V
-200mV
200mV
Time
505.0us 510.0us
V(COMP)
0V
-1.0V
1.0V
Class D amplifier circuit are simulated and compared with measured waveforms from oscilloscope
(Tektronix: TDS3054B)
Time
0s 0.3ms 0.7ms
V(OUT)
-4.0V
0V
4.0V
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
42
Time
1.988ms 1.990ms 1.992ms 1.994ms 1.996ms 1.998ms
V(VS)
-40V
-30V
-20V
-10V
0V
10V
20V
30V
40V
OUT
VS
Simulated Measured
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
43
Time
1.988ms 1.990ms 1.992ms 1.994ms 1.996ms 1.998ms
V(HO)
-40V
-30V
-20V
-10V
0V
10V
20V
30V
40V
Time
1.992ms 1.994ms 1.996ms 1.998ms 2.000ms 2.002ms
V(LO)
-40V
-30V
-20V
-10V
0V
10V
20V
30V
40V
HO
LO
Simulated Measured
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
44
Self-oscillation frequency = 400kHz (Simulated)
Self-oscillation frequency = 400kHz (Measured)
Simulated Measured
OUT OUT
VS VS
Self-Oscillating Frequency
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
+
-
SPEAKERF120A
FET1IRFIZ24N
FET2IRFIZ24N
+
C1EKMG500ELL100ME11D
C6AMZ0050J102C3
RPER11H103K2K1A01B
V1
FREQ = 1kVAMPL = 0VOFF = 0
0
C41nF
+B15V
+
C18EKMG500ELL222MLP1S
C51nF
0
R1810
0
R192.2k
C14MMH250K684
R4220
C710uIC = 10
R2
3kR1100k
C10 22uIC = 15
OUT
C922uIC = 12.85
MUR120RLG
D2
VS
IN
R1310
R3
47k
L17G14N-220-RB
VB
R171
0
R218.2k
R20
3.3k
R8
820
+B
VREF
VAA
0
R6 8.2k
R71.2k
CSD
OCSET
IN-
IC1
IRS2092
VAA
GND
IN-
COMP
CSD
VSS
VREF
OCSET DT
COM
LO
VCC
VS
HO
VB
CSH
VCC
0
DT
VSS 0
COMP
HO
R5
820
-B
R15
10
LO
VR175
-B-15V
0
C210uIC = 7
C810uIC = 7
R1110k
CSH
VS
C13MMC400K104
0
C12MMC250K474
R16
10
C11RPER11H104K2K1A01B
C15RPER11H104K2K1A01B
0Ls1
20nH
1
2
Ls2
20nH
1
2
Ls320nH
1
2
Ls420nH
1
2
R144.7
MUR120RLGD1
0
R9
4.7k
+
C16EKMG500ELL222MLP1S
Ls520nH
12
C17RPER11H104K2K1A01B
R1210k
Dead-time
45
Dead-time Mode R20 R21
DT1 (25ns) 3.3k 8.2k
DT2 (40ns) 5.6k 4.7k
DT3 (65ns) 8.2k 3.3k
DT4 (105ns) - < 10k
V(DT) Voltage Divider
Analysis Time Domain (Transient) Run to time: 1ms Start saving data after: 0.5m Maximum step size: 40n Skip the initial transient bias point calculation (SKIPBP)
.Options RELTOL: 0.001 VNTOL: 1.0u ABSTOL: 1.0n CHGTOL: 0.01p GMIN: 1.0E-12 ITL1: 500 ITL2: 200 ITL4: 10
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Dead-time DT1(25ns)
46
Time
0.9976ms 0.9980ms 0.9984ms 0.9988ms 0.9992ms0.9974ms
V(LO,-B) V(HO,VS)
-4V
0V
4V
8V
12V
16V
V(OUT)
0V
-400mV
400mV
SEL>>
DT1(25ns)
DT1(25ns)
Spike voltage
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Dead-time DT3(65ns)
47
Time
0.9976ms 0.9980ms 0.9984ms 0.9988ms 0.9992ms 0.9996ms
V(LO,-B) V(HO,VS)
-4V
0V
4V
8V
12V
16V
V(OUT)
0V
-400mV
400mV
SEL>>
DT3(65ns)
DT3(65ns)
Spike voltages (Decrease for longer dead time)
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
+
C1EKMG500ELL100ME11D
C6AMZ0050J102C3
RPER11H103K2K1A01B
C17RPER11H104K2K1A01B
+
C18EKMG500ELL222MLP1S
FET1IRFIZ24N
FET2IRFIZ24N
+
-
SPEAKERF120A
0
C41nF
+B15V
C51nF
0
R1810
0
R192.2k
C14MMH250K684
R4220
C710uIC = 10
R2
3kR1100k
C10 22uIC = 15
OUT
C922uIC = 12.85
MUR120RLG
D2
VS
IN
R1310
R3
47k
L17G14N-220-RB
VB
R171
0
R20
3.3k
R218.2k
R8
820
+B
VREF
VAA
0
R6 8.2k
R71.2k
CSD
OCSET
IN-
IC1
IRS2092
VAA
GND
IN-
COMP
CSD
VSS
VREF
OCSET DT
COM
LO
VCC
VS
HO
VB
CSH
V1
FREQ = 1kVAMPL = 0VOFF = 0
VCC
0
DT
VSS 0
COMP
HO
R5
820
-B
R15
10
LO
VR175
-B-15V
0
C210uIC = 7
C810uIC = 7
R1110k
CSH
VS
C13MMC400K104
0
C12MMC250K474
R16
10
C11RPER11H104K2K1A01B
C15RPER11H104K2K1A01B
0Ls1
20nH
1
2
Ls2
20nH
1
2
Ls320nH
1
2
Ls420nH
1
2
R144.7
MUR120RLGD1
0
R9
4.7k
+ C16EKMG500ELL222MLP1S
Ls520nH
12
R1210k
The total power loss in MOSFET are given by:
PTOTAL = PSW+Pcond+Pgd
48
Power losses in the MOSFETs
Analysis Time Domain (Transient) Run to time: 500us Start saving data after: 100n Maximum step size: 2n Skip the initial transient bias point calculation (SKIPBP)
.Options RELTOL: 0.003 VNTOL: 1.0m ABSTOL: 100n CHGTOL: 0.01p GMIN: 1.0E-12 ITL1: 500 ITL2: 200 ITL4: 20
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
23.6us 24.4us 25.2us 26.0us 26.8us 27.6us
1 V(FET1:S,FET1:D) 2 -I(Ls1) 3 V(FET1:D,FET1:S)*-I(Ls1)
0V
100V
-60V
1
-1.5A
-1.0A
-0.5A
0A
0.5A
1.0A
1.5A
2.0A
2.5A2
>>
-50W
0W
20W3
Power losses FET1(Professional Model)
49
FET1: ID and VDS are simulated and compared with scope (Tektronix: TDS3054B) waveforms
PSW ,Pcond ,and Pgd are calculated by PSpice.
VDS, ID (Measured)
-VDS
ID
-VDS
ID
Power loss (VDS*ID)
PSW Pgd Pcond
VDS, ID (Simulated)
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
492.8us 493.6us 494.4us 495.2us 496.0us
1 V(FET2:D,FET2:S) 2 -I(Ls3:1) 3 V(FET2:D,FET2:S)*-I(Ls3:1)
0V
100V
-40V
1
-1.0A
-0.5A
0A
0.5A
1.0A
1.5A
2.0A
2.5A
3.0A2
>>
-50W
0W
20W3
Power losses FET2(Professional Model)
50
FET2: ID and VDS are simulated and compared with scope (Tektronix: TDS3054B) waveforms
PSW ,Pcond ,and Pgd are calculated by PSpice.
VDS
ID
VDS
ID
Power loss (VDS*ID)
PSW Pgd Pcond
VDS, ID (Measured) VDS, ID (Simulated)
3.2 D級アンプ
Copyright (C) Bee Technologies Inc. 2013
• Gate charge characteristics in Professional model has more accurate results than standard model.
FET: IRFIZ24N Qg Standard vs. Professional Model
51
IRFIZ24N (Standard)
IRFIZ24N (Professional)
VDD=44V,ID=10A
,VGS=10V Measurement Simulation Error (%)
Standard Model: Qg(nc) 13.400 12.543 -6.396
Professional Model: Qg(nc) 13.400 13.409 0.067
3.2 D級アンプ
Copyright (C) Bee Technologies Inc. 2013
Time
867us 869us 871us 873us 875us 877us
1 V(OUT) 2 V(VS)
-1.0V
-0.5V
0V
0.5V
1.0V
1.5V
2.0V
2.5V
3.0V1
>>
-120V
-80V
-40V
0V
40V2
52
Simulated (without output capacitor models) Measured
OUT OUT
VS VS
Self-oscillation frequency = 400kHz (Simulated)
Self-oscillation frequency = 400kHz (Measured)
Simulation Result (without Capacitor Model)
3.2 D級アンプ
Copyright (C) Bee Technologies Inc. 2013
53
Simulated (with output capacitor models) Measured
OUT OUT
VS VS
Self-oscillation frequency = 400kHz (Simulated)
Self-oscillation frequency = 400kHz (Measured)
Simulation Result (with Capacitor Model)
D級アンプ
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Application Circuit
54
O_A
O_A1
O_B1
O_BO_B
RRSA 0.5ohmO_B1
V5Vref AB1.25Vdc
O_A1
O_A
RSB
L2
IC = 0
1
2
0
Cv ref AB1uF
00
L1
IC = 012
RSA
RRSB 0.5ohm
0
VM124V CVM1
100uF
00
U1
TB62206FG
CCP1 = 0.22UFCCP2 = 0.01UF
VM = 24COSC = 560PFROSC = 3.6K
FIN
CRVDDVREF_AVREF_BRS_B
RS_AVMCCP_CCCP_BCCP_A STANDBY
OUT_A1PHASE_APHASE_B
OUT_A
OUT_BENABLE_AENABLE_B
OUT_B1TORQUE
V_PHASE_A
TD = 0
TF = {tf phase}PW = {pwphase}PER = {tphase}
V1 = 0
TR = {trphase}
V2 = 5V
V_PHASE_B
TD = {tphase/4}
TF = {tf phase}PW = {pwphase}PER = {tphase}
V1 = 0V
TR = {trphase}
V2 = 5
0 0
PARAMETERS:
f phase = 250Hz
tphase = {1/f phase}
tdphase = {trphase+pwphase/2}
pwphase = {-2*trphase+tphase/2}
trphase = 100n
tf phase = {trphase}
VDD5Vdc C1
10uF
0 0
Rosc 3.6kohm
0
Cosc 560pF
0
Cccp_10.22uF
Cccp_20.022uF
250Hz Full Step
Ph_BPh_A
Ph_B
Ph_A
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
O_B1
O_B
O_A
O_A1
RSB 7.9ohm
L29.15mHIC = -0.5
1
2
L19.15mHIC = -0.5
12
RSA7.9ohm
O_A
O_A1
O_B1
O_B
RRSA 0.5ohm
V5Vref AB1.25Vdc
0
Cv ref AB1uF
00
RRSB 0.5ohm
0
VM124V CVM1
100uF
00
U1
TB62206FG
CCP1 = 0.22UFCCP2 = 0.01UF
VM = 24COSC = 560PFROSC = 3.6K
FIN
CRVDDVREF_AVREF_BRS_B
RS_AVMCCP_CCCP_BCCP_A STANDBY
OUT_A1PHASE_APHASE_B
OUT_A
OUT_BENABLE_AENABLE_B
OUT_B1TORQUE
V_PHASE_A
TD = {tphase/4}
TF = {tf phase}PW = {pwphase}PER = {tphase}
V1 = 0
TR = {trphase}
V2 = 5V
V_PHASE_B
TD = {tphase/2}
TF = {tf phase}PW = {pwphase}PER = {tphase}
V1 = 0V
TR = {trphase}
V2 = 5
0 0
PARAMETERS:
f phase = 250Hz
tphase = {1/f phase}
tdphase = {trphase+pwphase/2}
pwphase = {-2*trphase+tphase/2}
trphase = 100n
tf phase = {trphase}
VDD5Vdc C1
10uF
0 0
Rosc 3.6kohm
Cosc 560pF
0
0
Cccp_10.22uF
Cccp_20.022uF
250Hz Full Step
Ph_BPh_A
Ph_B
Ph_AFull Step Switching Sequence
55
Full-step sequences control signals
Analysis Time Domain (Transient) Run to time: 8ms Start saving data after: 0ms Maximum step size: -
.Options RELTOL: 0.01 VNTOL: 1.0m ABSTOL: 1.0n CHGTOL: 1p GMIN: 1.0E-12 ITL1: 500 ITL2: 200 ITL4: 100
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Full Step Switching Sequence
56
• This figure shows the simulation result of the circuit with Full-step switching sequence.
Phase A
Phase B
Enable A
Enable B
IOUT A
IOUT B
Time
0s 4.0ms 8.0ms
I(U1:OUT_B1)
-1.0A
0A
1.0A
I(U1:OUT_A1)
-1.0A
0A
1.0A
V(U1:ENABLE_B)
0V
SEL>>
V(U1:ENABLE_A)
0V
V(PH_B)
0V
V(PH_A)
0V
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
2.54ms 2.58ms
I(U1:OUT_B1)
400mA
600mA
I(U1:OUT_A1)
400mA
600mA
SEL>>
Output Ripple Current
• This figure shows the output ripple current of the Mixed Decay Mode ,which consist of Charge ,Slow decay ,and Fast decay mode ,with 101kHz chopping frequency.
57
IOUT = 0.5A
fchop = 101kHz
IOUT A
IOUT B Charge mode
Slow decay mode Fast decay mode
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
2.593ms 2.595ms 2.597ms 2.599ms 2.601ms 2.603ms
I(U1:OUT_A1)
300mA
400mA
500mA
600mA
700mA
SEL>>
Ripple Current Simulation
• The simulation result shows the current ripple that agrees to the measurement data.
58
Current ripple
Current ripple
Simulation
Measurement
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Parameter Settings
If there is no measurement data, the default value will be used:
Rm: motor winding resistance []
Lm: motor winding inductance [H]
Data is given by D.C. motor spec-sheet:
V_norm: normal voltage [V]
mNm: normal load [mNm]
kRPM_norm: speed at normal load [kr/min]
I_norm: current at normal load [A]
Load Condition:
IL: load current [A]
59
Model Parameters:
D.C. Motor model and Parameters with Default Value
-+
U1SMPL_DC_MOTORRm = 0.1Lm = 100u
I_norm = 6.1
mNm = 19.6V_norm = 7.2
kRPM_norm = 14.4
IL = 6.1
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
60
Time
0s 40ms 80ms 120ms 160ms 200ms 240ms 280ms 320ms 360ms 400ms
I(VIM)
0A
10A
20A
V(VM)
0V
5V
10V
SEL>>
I(X_U1.V_kRPM)
0A
10A
20A
V(X_U1.TRQ)
0V
40V
80V
D.C. Motor Current = 6.1A
D.C. Motor Voltage = 7.2V
D.C. Motor Speed = 14.4krpm
Torque Load= 19.6mNm
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
0s 40ms 80ms 120ms 160ms 200ms 240ms 280ms 320ms 360ms 400ms
I(VIM)
0A
10A
20A
V(VM)
0V
5V
10V
I(X_U1.V_kRPM)
0A
10A
20A
SEL>>
V(X_U1.TRQ)
0V
40V
80V
61
D.C. Motor Current = 3.05A
D.C. Motor Voltage = 8.725V
D.C. Motor Speed = 18.4krpm
Torque Load= 9.8mNm
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
-+
U2SMPL_DC_MOTORRm = 0.576Lm = 165u
I_norm = 2.9
mNm = 9.8V_norm = 7.2
kRPM_norm = 14.2
IL = 0.6NC
NC
NCA
K
VCC
VO
GND
U1
TLP350
V1
TD = 0
TF = 10nPW = 199.99uPER = 400u
V1 = 0
TR = 10n
V2 = 1.8
0
R11u
0
Vcc
15V
0
VCC
VDD
0
RG120
0
DGT10J321_s
D3
VCC
Vdd
15V
VDD
0
D4001D2
U3GT10J321
62
Simplified D.C. Motor with RS-380PH Spec at No load.
Simulation Circuit and Setting
No load IL=0.6
Application Example
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
-100ms 0s 100ms 300ms 500ms 700ms 900ms
1 I(U2:1) 2 V(U2:1,U2:2)
-2A
0A
2A
4A
6A
8A
10A
12A
14A1
-60V
-50V
-40V
-30V
-20V
-10V
0V
10V
20V2
>>
Application Example
63
Measurement Simulation
Motor Current (2A/Div)
Motor Voltage (10V/Div)
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
Time
898.0ms 898.4ms 898.8ms 899.2ms 899.6ms
1 I(U3:C) 2 V(U3:C) 3 V(U3:G)
-2A
0A
2A
4A
6A
8A
10A
12A
14A1
>>
-30V
-20V
-10V
0V
10V
20V
30V
40V
50V2
-60V
-50V
-40V
-30V
-20V
-10V
0V
10V
20V3
Application Example
64
Measurement Simulation
IGBT: VGE
IGBT: VCE
IGBT: IC
IGBT: VGE (10V/Div)
IGBT: VCE (10V/Div)
IGBT: IC (2A/Div)
ステッピングモータ制御回路
3.SPICEの再現性を高める方法
Copyright (C) Bee Technologies Inc. 2013
4. 収束エラー改善方法について
65 Copyright (C) Bee Technologies Inc. 2013
(1)解析の刻みを変更する →刻みを荒くする (2).OPTIONSで改善する →それぞれのパラメータで改善する (3)回路で改善する →スナバ回路等を追加する
4. 収束エラー改善方法について
66 Copyright (C) Bee Technologies Inc. 2013
4. 収束エラー改善方法について
67 Copyright (C) Bee Technologies Inc. 2013
4. 収束エラー改善方法について
68 Copyright (C) Bee Technologies Inc. 2013
パラメータ 単位 説明
RELTOL 電圧及び電流の相対精度
VNTOL V 電圧の最高精度
ABSTOL A 電流の最高精度
CHGTOL Q 電荷の最高精度
GMIN 1/Ω 全ての分岐の最小コンダクタンス
ITL1 DC、バイパスの繰り返し上限(予測なし)
ITL2 DC、バイパスの繰り返し上限(予測あり)
ITL4 過渡の時間ポイントの繰り返し制限
4. 収束エラー改善方法について
69 Copyright (C) Bee Technologies Inc. 2013
パラメータ 対処
ITL1 バイパスポイントを解析中に収束エラー発生時に対処
ITL2 DC解析中に収束エラー発生時に対処
ITL4 過渡解析中に収束エラー発生時に対処
ITLの対処方法
パワーエレクトロニクス分野の解析の場合
パラメータ 対処
VNTOL 大電圧の場合に対処
ABSTOL 大電流の場合に対処
4. 収束エラー改善方法について
70 Copyright (C) Bee Technologies Inc. 2013
Standard Default
.OPTIONS RELTOL=0.001 VNTOL=1.0u ABSTOL=1.0p CHGTOL=0.01p GMIN=1.0E-12 ITL1=150 ITL2=20 ITL4=10
Simulation Convergence Quick Fix
.OPTIONS RELTOL=0.01 VNTOL=1.0m ABSTOL=1.0n CHGTOL=0.01u GMIN=1.0E-12 ITL1=500 ITL2=200 ITL4=100
71 Copyright (C) Bee Technologies Inc. 2013
質疑・応答